System and method for analyzing a frequency response of an electromagnetic cooking device

ABSTRACT

A method for analyzing a frequency response of a cooking device is disclosed. The method comprises controlling a plurality of RF signals within an operating range of the cooking device at plurality of phase shifts between a first RF signal and a second RF signal. A plurality of efficiencies of at least one reflection signal in the resonant cavity are measured in response to a plurality of RF feeds generated from the RF signals for the plurality of phase shifts. The frequency response of the resonant cavity is modeled with a numeric model and a plurality of interpolation parameters for the numeric model are calculated based on the plurality of measured efficiencies of the RF feeds. The frequency response of the cavity is estimated for the operating range of the cooking device based on the numeric model with the plurality of interpolation parameters.

BACKGROUND

The present device generally relates to a method and device forelectromagnetic cooking, and more specifically, to a method and devicefor determining and controlling the resonant modes within a microwaveoven.

A conventional microwave oven cooks food by a process of dielectricheating in which a high-frequency alternating electromagnetic field isdistributed throughout an enclosed cavity. A sub-band of the radiofrequency spectrum, microwave frequencies at or around 2.45 GHz causedielectric heating primarily by absorption of energy in water.

To generate microwave frequency radiation in a conventional microwave, avoltage applied to a high-voltage transformer results in a high-voltagepower that is applied to a magnetron that generates microwave frequencyradiation. The microwaves are then transmitted to an enclosed cavitycontaining the food through a waveguide. Cooking food in an enclosedcavity with a single, non-coherent source like a magnetron can result innon-uniform heating of the food. To more evenly heat food, microwaveovens include, among other things, mechanical solutions such as amicrowave stirrer and a turntable for rotating the food. A commonmagnetron-based microwave source is not narrowband and not tunable (i.e.emits microwaves at a frequency that is changing over time and notselectable). As an alternative to such a common magnetron-basedmicrowave source, solid-state sources can be included in microwave ovenswhich are tunable and coherent.

SUMMARY

In one aspect of the disclosure, a method for analyzing a frequencyresponse of an electromagnetic cooking device comprising a resonantcavity is disclosed. The method comprises controlling a plurality of RFsignals comprising a first RF signal and a second RF signal within anoperating range of the cooking device at plurality of phase shiftsbetween the first RF signal and the second RF signal. The method furthercomprises measuring a plurality of efficiencies of at least onereflection signal in the resonant cavity in response to a plurality ofRF feeds generated from the RF signals for the plurality of phaseshifts. The frequency response of the resonant cavity is modeled with anumeric model and a plurality of interpolation parameters for thenumeric model are calculated based on the plurality of measuredefficiencies of the RF feeds in response to the plurality of phaseshifts. The frequency response of the cavity is estimated for theoperating range of the cooking device based on the numeric model withthe plurality of interpolation parameters.

In another aspect of the disclosure, an electromagnetic cooking deviceis disclosed. The device comprises an enclosed cavity configured toreceive a food load and a plurality of amplifiers configured amplify afirst RF signal and a second RF signal thereby supplying a plurality ofRF feeds to the enclosed cavity. At least one measurement device isconfigured to measure a plurality of reflection signals from the RFfeeds. A controller is in communication with the plurality of amplifiersand the measurement device.

The controller is configured to control the first RF signal and thesecond RF signal within an operating range of the cooking device atplurality of phase shifts between the first RF signal and the second RFsignal. The controller is further configured to control the amplifiersto amplify the RF signals thereby generating the plurality of RF feedsand measure a plurality of efficiencies of the reflection signals in thecavity induced by the RF feeds for the plurality of phase shifts. Thecontroller is further configured to estimate efficiency results for thefrequency response of the cavity comprising additional phase shiftsestimated for the operating range of the cooking device. The additionalphase shifts are different from the plurality of phase shifts.

In yet another aspect of the disclosure, an electromagnetic cookingdevice is disclosed. The device comprises an enclosed cavity configuredto receive a food load and a plurality of amplifiers configured amplifya first RF signal and a second RF signal thereby supplying a pluralityof RF feeds to the enclosed cavity. At least one measurement device isconfigured to measure a plurality of reflection signals from the RFfeeds. A controller is in communication with the plurality of amplifiersand the measurement device.

The controller is configured to control the first RF signal and thesecond RF signal within an operating range of the cooking device at aplurality of phase shifts between the first RF signal and the second RFsignal. The controller is further configured to control the amplifiersto amplify the RF signals thereby generating a plurality of RF feeds andmeasure a plurality of efficiencies of the reflection signals in thecavity induced by the RF feeds for the plurality of phase shifts. Thecontroller is further configured to model the frequency response of thecavity with a numeric model and calculate a plurality of interpolationparameters for the numeric model based on the plurality of measuredefficiencies. The controller is further configured to generate estimatedefficiency results with the numeric model for a frequency response ofthe cavity. The estimated efficiency results comprise additional phaseshifts estimated for the operating range of the cooking device and theadditional phase shifts are different from the plurality of phaseshifts.

BRIEF DESCRIPTION OF THE DRAWINGS

In the drawings:

FIG. 1 is a block diagram of an electromagnetic cooking device withmultiple coherent radio frequency feeds in accordance with variousaspects described herein;

FIG. 2 is a block diagram of a radio frequency signal generator of FIG.1;

FIG. 3 is a schematic diagram illustrating a high-power radio frequencyamplifier coupled to a waveguide in accordance with various aspectsdescribed herein;

FIG. 4 is a cross-sectional diagram illustrating an integratedcirculator for use in a high-power radio frequency amplifier inaccordance with various aspects described herein;

FIG. 5 is a top-view diagram illustrating the integrated circulator ofFIG. 4;

FIG. 6 is a schematic diagram illustrating a high-power radio frequencyamplifier coupled to a waveguide with an integrated measurement systemin accordance with various aspects described herein;

FIG. 7 is a schematic diagram illustrating a high-power radio frequencyamplifier coupled to a waveguide with an integrated measurement systemincluding a reflectometer in accordance with various aspects describedherein;

FIG. 8 is a flowchart illustrating a binary control routine forcontrolling the output power of high-power amplifiers;

FIG. 9 is a schematic diagram illustrating a resonant cavity coupled totwo radio frequency waveguides in accordance with various aspectsdescribed herein;

FIG. 10 is a graphical diagram illustrating efficiency versus frequencyfor in-phase and antiphase excitations of the resonant cavity of FIG. 8;

FIG. 11 is a diagram illustrating features of a method of analysis todetermine the resonant modes of the cavity in accordance with variousaspects described herein;

FIG. 12 is a diagram illustrating features of a method to characterizethe resonant modes of the cavity in accordance with various aspectsdescribed herein;

FIGS. 13A and 13B are schematic diagrams illustrating features of amethod to locate and classify foodstuff positioned within a resonantcavity in accordance with various aspects described herein;

FIG. 14 is a graphical diagram illustrating efficiency versus frequencyfor in-phase excitations of the resonant cavity of FIG. 8 showing the Qfactors;

FIG. 15 is a diagram illustrating features of a method to characterizethe unbalanced resonant modes of the cavity in accordance with variousaspects described herein;

FIG. 16 is a diagram illustrating features of a method to characterizethe balanced resonant modes of the cavity in accordance with variousaspects described herein;

FIG. 17 is a flowchart illustrating a method of exciting an enclosedcavity with radio frequency radiation in accordance with various aspectsdescribed herein;

FIG. 18 is a diagram illustrating features of a method to characterizethe unbalanced resonant modes of the cavity when a non-centered foodload is present in accordance with various aspects described herein;

FIG. 19 is a diagram illustrating features of a method to characterizethe balanced resonant modes of the cavity when a non-centered food loadis present in accordance with various aspects described herein;

FIG. 20 are plots of the phase vs efficiency curves of one example fortwo symmetries;

FIG. 21 are plots of the phase vs efficiency curves of another examplefor two symmetries;

FIG. 22 is a block diagram illustrating an open-loop regulation of aheating strategy synthesis;

FIG. 23 is a block diagram illustrating a closed-loop regulation of aheating strategy synthesis;

FIG. 24 is a phase and frequency plot demonstrating an efficiencyresponse of a heating cavity and a stirring route for an electronicstirring operation;

FIG. 25A is an efficiency map of one example of a food load in theenclosed cavity where the cooking appliance includes two ports;

FIG. 25B is an efficiency map of one example of a food load in theenclosed cavity where the cooking appliance includes four ports;

FIG. 26A is an efficiency map of an example where the system is mostlysymmetric and most of the resonances are not rotated;

FIG. 26B is an efficiency map of an example where the system is mostlyasymmetric and most of the resonances are rotated;

FIG. 27 is a flowchart illustrating an alternative method of exciting anenclosed cavity with radio frequency radiation in accordance withvarious aspects described herein;

FIG. 28 is a flowchart illustrating a method of spectromodalidentification of resonant modes within the cooking cavity;

FIG. 29A is a schematic diagram of a heating cavity demonstrating aphase shift having an even symmetry;

FIG. 29B is a schematic diagram of a heating cavity demonstrating aphase shift having an odd symmetry;

FIG. 30 are graphic plots illustrating an example of adaptive filtering;

FIG. 31 is a flowchart illustrating a method of monitoring a food loadusing a coefficient of variation of the efficiency;

FIG. 32A illustrates sample data for an efficiency of a liquid beingheated in a cooking cavity during a still phase, a weak boiling state,and a strong boiling state;

FIG. 32B illustrates sample data for a coefficient of variationdetermined from the efficiency shown in in FIG. 32A;

FIG. 33 is a flowchart illustrating a method of heating the liquid basedon the coefficient of variation of efficiency and the threshold shown inFIG. 31B;

FIG. 34 is flowchart illustrating and alternative method of heating theliquid based on the coefficient of variation of efficiency and the maskshown in FIG. 31C;

FIG. 35 illustrates sample data for the coefficient of variation ofefficiency for milk heated in the cooking cavity;

FIG. 36 is a flowchart illustrating a method of heating milk based onthe coefficient of variation of efficiency and a threshold indicative ofa user-specified temperature;

FIG. 37 is a flowchart illustrating a method of melting a food loadbased on changes in resonances and the coefficient of variation ofefficiency;

FIG. 38 illustrates sample data for the coefficient of variation ofefficiency for a sauce heated in the cavity;

FIG. 39 is a flowchart illustrating a method of heating the sauce basedon the coefficient of variation of efficiency and a threshold indicativeof a boiling state of the sauce;

FIG. 40 illustrates sample data for the coefficient of variation ofefficiency for popcorn being popped in the cavity;

FIGS. 41 and 42 are flowcharts illustrating a method of popping popcornbased on the coefficient of variation of efficiency and a thresholdindicative of a popping state of popcorn;

FIG. 43 is a flowchart illustrating a method of monitoring a food loadusing a Q-factor;

FIG. 44A is a plot demonstrating a relative permittivity for a breadbased food load;

FIG. 44B is a plot demonstrating a loss tangent for a bread based foodload;

FIG. 44C is a plot demonstrating a Q-factor for a bread based food load;

FIG. 45A is a plot demonstrating a relative permittivity for a potatobased food load;

FIG. 45B is a plot demonstrating a loss tangent for a potato based foodload;

FIG. 45C is a plot demonstrating a Q-factor for a potato based foodload;

FIG. 46A is a plot demonstrating a relative permittivity for a meatbased food load;

FIG. 46B is a plot demonstrating a loss tangent for a meat based foodload;

FIG. 46C is a plot demonstrating a Q-factor for a meat based food load;and

FIG. 47 is a flow chart of a method of identifying a level of donenessbased on a Q-factor in accordance with the disclosure.

DETAILED DESCRIPTION

It is to be understood that the specific devices and processesillustrated in the attached drawings, and described in the followingspecification are simply exemplary embodiments of the inventive conceptsdefined in the appended claims. Hence, other physical characteristicsrelating to the embodiments disclosed herein are not to be considered aslimiting, unless the claims expressly state otherwise.

A solid-state radio frequency (RF) cooking appliance heats up andprepares food by introducing electromagnetic radiation into an enclosedcavity. Multiple RF feeds at different locations in the enclosed cavityproduce dynamic electromagnetic wave patterns as they radiate. Tocontrol and shape of the wave patterns in the enclosed cavity, themultiple RF feeds can radiate waves with separately controlledelectromagnetic characteristics to maintain coherence (that is, astationary interference pattern) within the enclosed cavity. Forexample, each RF feed can transmit a different frequency, phase and/oramplitude with respect to the other feeds. Other electromagneticcharacteristics can be common among the RF feeds. For example, each RFfeed can transmit at a common but variable frequency. Although thefollowing embodiments are directed to a cooking appliance where RF feedsdirect electromagnetic radiation to heat an object in an enclosedcavity, it will be understood that the methods described herein and theinventive concepts derived therefrom are not so limited. The coveredconcepts and methods are applicable to any RF device whereelectromagnetic radiation is directed to an enclosed cavity to act on anobject inside the cavity. Exemplary devices include ovens, dryers,steamers, and the like.

FIG. 1 shows a block diagram of an electromagnetic cooking device 10with multiple coherent RF feeds 26A-D according to one embodiment. Asshown in FIG. 1, the electromagnetic cooking device 10 includes a powersupply 12, a controller 14, an RF signal generator 16, a human-machineinterface 28 and multiple high-power RF amplifiers 18A-D coupled to themultiple RF feeds 26A-D. The multiple RF feeds 26A-D each transfer RFpower from one of the multiple high-power RF amplifiers 18A-D into anenclosed cavity 20.

The power supply 12 provides electrical power derived from mainselectricity to the controller 14, the RF signal generator 16, thehuman-machine interface 28 and the multiple high-power RF amplifiers18A-D. The power supply 12 converts the mains electricity to therequired power level of each of the devices it powers. The power supply12 can deliver a variable output voltage level. For example, the powersupply 12 can output a voltage level selectively controlled in 0.5-Voltsteps. In this way, the power supply 12 can be configured to typicallysupply 28 Volts direct current to each of the high-power RF amplifiers18A-D, but can supply a lower voltage, such as 15 Volts direct current,to decrease an RF output power level by a desired level.

A controller 14 can be included in the electromagnetic cooking device10, which can be operably coupled with various components of theelectromagnetic cooking device 10 to implement a cooking cycle. Thecontroller 14 can also be operably coupled with a control panel orhuman-machine interface 28 for receiving user-selected inputs andcommunicating information to a user. The human-machine interface 28 caninclude operational controls such as dials, lights, switches, touchscreen elements, and displays enabling a user to input commands, such asa cooking cycle, to the controller 14 and receive information. The userinterface 28 can include one or more elements, which can be centralizedor dispersed relative to each other. The controller 14 may also selectthe voltage level supplied by power supply 12.

The controller 14 can be provided with a memory and a central processingunit (CPU), and can be preferably embodied in a microcontroller. Thememory can be used for storing control software that can be executed bythe CPU in completing a cooking cycle. For example, the memory can storeone or more pre-programmed cooking cycles that can be selected by a userand completed by the electromagnetic cooking device 10. The controller14 can also receive input from one or more sensors. Non-limitingexamples of sensors that can be communicably coupled with the controller14 include peak level detectors known in the art of RF engineering formeasuring RF power levels and temperature sensors for measuring thetemperature of the enclosed cavity or one or more of the high-poweramplifiers 18A-D.

Based on the user input provided by the human-machine interface 28 anddata including the forward and backward (or reflected) power magnitudescoming from the multiple high-power amplifiers 18A-D (represented inFIG. 1 by the path from each of the high-power amplifiers 18A-D throughthe RF signal generator 16 to the controller 14), the controller 14 candetermine the cooking strategy and calculate the settings for the RFsignal generator 16. In this way, one of the main functions of thecontroller 14 is to actuate the electromagnetic cooking device 10 toinstantiate the cooking cycle as initiated by the user. The RF signalgenerator 16 as described below then can generate multiple RF waveforms,that is, one for each high-power amplifier 18A-D based on the settingsindicated by the controller 14.

The high-power amplifiers 18A-D, each coupled to one of the RF feeds26A-D, each output a high power RF signal based on a low power RF signalprovided by the RF signal generator 16. The low power RF signal input toeach of the high-power amplifiers 18A-D can be amplified by transformingthe direct current electrical power provided by the power supply 12 intoa high power radio frequency signal. In one non-limiting example, eachhigh-power amplifier 18A-D can be configured to output an RF signalranging from 50 to 250 Watts. The maximum output wattage for eachhigh-power amplifier can be more or less than 250 Watts depending uponthe implementation. Each high-power amplifier 18A-D can include a dummyload to absorb excessive RF reflections.

The multiple RF feeds 26A-D transfer power from the multiple high-powerRF amplifiers 18A-D to the enclosed cavity 20. The multiple RF feeds26A-D can be coupled to the enclosed cavity 20 in spatially separatedbut fixed physical locations. The multiple RF feeds 26A-D can beimplemented via waveguide structures designed for low power losspropagation of RF signals. In one non-limiting example, metallic,rectangular waveguides known in microwave engineering are capable ofguiding RF power from a high-power amplifier 18A-D to the enclosedcavity 20 with a power attenuation of approximately 0.03 decibels permeter.

Additionally, each of the RF feeds 26A-D can include a sensingcapability to measure the magnitude of the forward and the backwardpower levels or phase at the amplifier output. The measured backwardpower indicates a power level returned to the high-power amplifier 18A-Das a result of an impedance mismatch between the high-power amplifier18A-D and the enclosed cavity 20. Besides providing feedback to thecontroller 14 and the RF signal generator 16 to implement, in part, acooking strategy, the backward power level can indicate excess reflectedpower that can damage the high-power amplifier 18A-D.

Along with the determination of the backward power level at each of thehigh-power amplifiers 18A-D, temperature sensing at the high-poweramplifier 18A-D, including at the dummy load, can provide the datanecessary to determine if the backward power level has exceeded apredetermined threshold. If the threshold is exceeded, any of thecontrolling elements in the RF transmission chain including the powersupply 12, controller 14, the RF signal generator 16, or the high-poweramplifier 18A-D can determine that the high-power amplifier 18A-D can beswitched to a lower power level or completely turned off. For example,each high-power amplifier 18A-D can switch itself off automatically ifthe backward power level or sensed temperature is too high for severalmilliseconds. Alternatively, the power supply 12 can cut the directcurrent power supplied to the high-power amplifier 18A-D.

The enclosed cavity 20 can selectively include subcavities 22A-B byinsertion of an optional divider 24 therein. The enclosed cavity 20 caninclude, on at least one side, a shielded door to allow user access tothe interior of the enclosed cavity 20 for placement and retrieval offood or the optional divider 24.

The transmitted bandwidth of each of the RF feeds 26A-D can includefrequencies ranging from 2.4 GHz to 2.5 GHz. The RF feeds 26A-D can beconfigured to transmit other RF bands. For example, the bandwidth offrequencies between 2.4 GHz and 2.5 GHz is one of several bands thatmake up the industrial, scientific and medical (ISM) radio bands. Thetransmission of other RF bands is contemplated and can includenon-limiting examples contained in the ISM bands defined by thefrequencies: 13.553 MHz to 13.567 MHz, 26.957 MHz to 27.283 MHz, 902 MHzto 928 MHz, 5.725 GHz to 5.875 GHz and 24 GHz to 24.250 GHz.

Referring now to FIG. 2, a block diagram of the RF signal generator 16is shown. The RF signal generator 16 includes a frequency generator 30,a phase generator 34 and an amplitude generator 38 sequentially coupledand all under the direction of an RF controller 32. In this way, theactual frequency, phases and amplitudes to be output from the RF signalgenerator 16 to the high-power amplifiers are programmable through theRF controller 32, preferably implemented as a digital control interface.The RF signal generator 16 can be physically separate from the cookingcontroller 14 or can be physically mounted onto or integrated into thecontroller 14. The RF signal generator 16 is preferably implemented as abespoke integrated circuit.

As shown in FIG. 2 the RF signal generator 16 outputs four RF channels40A-D that share a common but variable frequency (e.g. ranging from 2.4GHz to 2.5 GHz), but are settable in phase and amplitude for each RFchannel 40A-D. The configuration described herein is exemplary andshould not be considered limiting. For example, the RF signal generator16 can be configured to output more or less channels and can include thecapability to output a unique variable frequency for each of thechannels depending upon the implementation.

As previously described, the RF signal generator 16 can derive powerfrom the power supply 12 and input one or more control signals from thecontroller 14. Additional inputs can include the forward and backwardpower levels determined by the high-power amplifiers 18A-D. Based onthese inputs, the RF controller 32 can select a frequency and signal thefrequency generator 30 to output a signal indicative of the selectedfrequency. As represented pictorially in the block representing thefrequency generator 30 in FIG. 2, the selected frequency determines asinusoidal signal whose frequency ranges across a set of discretefrequencies. In one non-limiting example, a selectable bandwidth rangingfrom 2.4 GHz to 2.5 GHz can be discretized at a resolution of 1 MHzallowing for 101 unique frequency selections.

After the frequency generator 30, the signal is divided per outputchannel and directed to the phase generator 34. Each channel can beassigned a distinct phase, that is, the initial angle of a sinusoidalfunction. As represented pictorially in the block representing the perchannel phase generator 36A-D in FIG. 2, the selected phase of the RFsignal for a channel can range across a set of discrete angles. In onenon-limiting example, a selectable phase (wrapped across half a cycle ofoscillation or 180 degrees) can be discretized at a resolution of 10degrees allowing for 19 unique phase selections per channel.

Subsequent to the phase generator 34, the RF signal per channel can bedirected to the amplitude generator 38. The RF controller 32 can assigneach channel (shown in FIG. 2 with a common frequency and distinctphase) to output a distinct amplitude in the channel 40A-D. Asrepresented pictorially in the block representing the per channelamplitude generator in FIG. 2, the selected amplitude of the RF signalcan range across a set of discrete amplitudes (or power levels). In onenon-limiting example, a selectable amplitude can be discretized at aresolution of 0.5 decibels across a range of 0 to 23 decibels allowingfor 47 unique amplitude selections per channel.

The amplitude of each channel 40A-D can be controlled by one of severalmethods depending upon the implementation. For example, control of thesupply voltage of the amplitude generator 38 for each channel can resultin an output amplitude for each channel 40A-D from the RF signalgenerator 16 that is directly proportional to the desired RF signaloutput for the respective high-power amplifier 18A-D. Alternatively, theper channel output can be encoded as a pulse-width modulated signalwhere the amplitude level is encoded by the duty cycle of thepulse-width modulated signal. Yet another alternative is to coordinatethe per channel output of the power supply 12 to vary the supply voltagesupplied to each of the high-power amplifiers 18A-D to control the finalamplitude of the RF signal transmitted to the enclosed cavity 20.

As described above, the electromagnetic cooking device 10 can deliver acontrolled amount of power at multiple RF feeds 26A-D into the enclosedcavity 20. Further, by maintaining control of the amplitude, frequencyand phase of the power delivered from each RF feed 26A-D, theelectromagnetic cooking device 10 can coherently control the powerdelivered into the enclosed cavity 20. Coherent RF sources deliver powerin a controlled manner to exploit the interference properties ofelectromagnetic waves. That is, over a defined area of space andduration of time, coherent RF sources can produce stationaryinterference patterns such that the electric field is distributed in anadditive manner. Consequently, interference patterns can add to createan electromagnetic field distribution that is greater in amplitude thanany of the RF sources (i.e. constructive interference) or less than anyof the RF sources (i.e. destructive interference).

The coordination of the RF sources and characterization of the operatingenvironment (i.e. the enclosed cavity and the contents within) canenable coherent control of the electromagnetic cooking and maximize thecoupling of RF power with an object in the enclosed cavity 20. Efficienttransmission into the operating environment can require calibration ofthe RF generating procedure. As described above, in an electromagneticheating system, the power level can be controlled by many componentsincluding the voltage output from the power supply 12, the gain onstages of variable gain amplifiers including both the high-poweramplifiers 18A-D and the amplitude generator 38, the tuning frequency ofthe frequency generator 30, etc. Other factors that affect the outputpower level include the age of the components, inter-componentinteraction and component temperature.

Referring now to FIG. 3, a schematic diagram illustrating a high-poweramplifier 18 coupled to a waveguide 110 in accordance with variousaspects described herein is shown. The high-power amplifier 18 includesone or more amplification stages 100 coupled via a guiding structure 102to a circulator 104. The circulator 104 is coupled by a guidingstructure 106 to a waveguide exciter 108. The high-power amplifier 18 iselectrically coupled to the waveguide 110 by the waveguide exciter 108and mechanically coupled by an electromagnetic gasket 112.

The high-power amplifier 18 is configured such that a number ofamplification stages 100 are interconnected to amplify a radio frequencysignal from the amplifier input to the amplifier output. Theamplification stages 100 include one or more transistors configured toconvert a small change in input voltage to produce a large change inoutput voltage. Depending upon the configuration of the circuit, theamplification stages 100 can produce a current gain, a voltage gain orboth.

The output of the amplification stages 100 is coupled to the circulator104 via a guiding structure 102. The guiding structure 102 can be anyelectrical connector capable of carrying high-power radio frequencysignal including but not limited to a microstrip printed on a dielectricsubstrate of a printed circuit board. The circulator 104 is a passivemulti-port component that transmits radio frequency signals from oneport to the next where a port is a point on the circulator 104 forcoupling a radio frequency signal from one component to another. In thehigh-power amplifier 18, the circulator 104 acts as a protective deviceto isolate the amplification stages 100 from deleterious effects thatcan occur when a mismatched load reflects power.

The circulator 104 is coupled to the waveguide exciter 108 via theguiding structure 106. The high-power amplifier 18 is terminated at itsoutput by the waveguide exciter 108. The waveguide exciter 108 convertselectromagnetic energy from a first mode suitable for transmissionwithin the high-power amplifier 18 to a second mode suitable fortransmission within the waveguide 110. In this way, the waveguide 110acts as an RF feed 26A-D to convey the amplified electromagnetic signalfrom the high-power amplifier to the microwave cavity.

The electromagnetic gasket 112 provides a secure connection between thehigh-power amplifier 18 and the waveguide 110 and surrounds the portionof the waveguide exciter 108 positioned between the high-power amplifier18 and the waveguide 110. The electromagnetic gasket 112 can be formedof one or more materials useful for securing the connection between thehigh-power amplifier 18 and the waveguide 110 and providingelectromagnetic shielding at radio frequencies. Such materials caninclude, but are not limited to, silicone-based constituents filled withconductive particles such as silver or nickel.

The provision of the waveguide exciter 108 that terminates the output ofthe high-power amplifier 18 reduces the electromagnetic losses typicallyincurred at the junction of microwave devices coupled via conventionalconnectors. That is, conventional microwave devices are interconnectedvia coaxial connectors (e.g. BNC or N-type connectors) that incur RFlosses due to the additional path lengths for the connectors as well asthe losses at the coupling of the coaxial connectors. Theelectromagnetic gasket 112 augments the efficiency of the waveguideexciter 108 by shielding the waveguide exciter 108 as well as providingthe mechanical support of the coupling between the high-power amplifier18 and the waveguide 110.

Referring now to FIG. 4, a cross-sectional side view illustrating thecirculator 104 in accordance with various aspects described herein isshown. As described above, the circulator 104 is coupled to the outputof the amplification stages via the guiding structure 102. Thecirculator 104 includes a laminate 122 mounted to a metal base plate120.

Two ferrite magnets 126, 128 in axial alignment perpendicular to thelaminate 122 are secured to the laminate 122 by clips 130. The ferritemagnets 126, 128 can be any shape suitable for the circulator design,including, but not limited to a disk.

The guiding structure 102 can include a microstrip that is printed on alaminate 122. The laminate 122 is a dielectric substrate that caninclude any material suitable for the provision of insulating layers ofa printed circuit board including, but not limited to, FR-2 material orFR-4 material. The laminate 122 is positioned on the metal base plate120 that provides mechanical support to the circulator 104.Additionally, the metal base plate 120 acts as a thermal dissipatingmass and to spread heat generated by the circulator 104. The metal baseplate 120 includes a pocket 124 to house the lower ferrite magnet 128.

During the manufacturing of the circulator 104, the lower ferrite magnet128 is placed in the pocket 124 of the metal base plate 120. Thelaminate 122 and microstrip guiding structure are applied to the metalbase plate 120. The upper ferrite magnet 126 is placed above lowerferrite magnet 128 and secured to the laminate 122 by clips 130.

FIG. 5 is a top-view diagram illustrating the integrated circulator ofFIG. 4. As described, the circulator 104 includes, as part of itsmagnetic circuit, the laminate 122 of a printed circuit board as well asthe microstrip guiding structure 102 coupled to the output of theamplification stages (cf. element 100 in FIG. 3). In this way, thecirculator 104 does not include input or output pins that require asoldered connection during the manufacturing process. Conventionalsolder joints can expose the high-power amplifier to reliability issuesbecause the soldering process can result in cold-spots or bad couplings.Therefore, the circulator 104 is not a conventional discrete componentsoldered in the high-power amplifier. Instead the circulator 104 isdirectly integrated as a component of the high-power amplifier.

For the output power level at the end of the amplification stages 100 tohit a desired set-point level, the RF signal generator (cf. element 16in FIG. 1) can rely on feedback in the form of signals indicative of theforward and backward power levels or the relative phases of the radiofrequency signals conveyed to the enclosed cavity (cf. element 20 inFIG. 1). Therefore, in addition to the amplifying components foroutputting a radio frequency signal that is amplified in power withrespect to an input radio frequency signal, conventional high-poweramplifiers can include a measuring component that outputs a signalindicative of the radio frequency power transmitted and received by theamplifying component. However, by integrating such a measurementcomponent within the high-power amplifier, the output stage of ahigh-power amplifier can incur electrical losses that can reduce thepower and fidelity of the radio frequency signal output to the radiofrequency feed (cf. elements 26A-D in FIG. 1) such as a waveguide.

Referring now to FIG. 6, schematic diagram illustrating a high-poweramplifier 18 coupled to a waveguide 110 with an integrated measurementsystem 150 in accordance with various aspects described herein is shown.The integrated measurement system 150 includes probe antennas 152coupled to electronic components 154. The probe antennas 152 includeportions located within the waveguide 110 that convert radio frequencyelectromagnetic waves within the waveguide 110 into an analog electricpower signal. The probe antennas 152 can be any type of antenna usefulfor measuring radio frequency electromagnetic waves within a waveguide,including but not limited to, dipole antennas.

The electronic components 154 are coupled to the probe antennas 152 andcan include an analog-to-digital convertor (ADC) such that the outputsignal is digital and readily input to a device such as the RF signalgenerator (cf. element 16 in FIG. 1), controller (cf. element 14 inFIG. 1) or the RF controller (cf. element 32 in FIG. 1). The electroniccomponents 154 can be any component useful for the measurement of radiofrequency signals including, but not limited to, radio frequency logpower detectors that provide a direct current output voltage that islog-linear with respect to the detected radio frequency power levelwithin the waveguide 110.

The measurement system can include additional components useful forfurther characterizing the radio frequency transmissions conveyedthrough the waveguide 110. Referring now to FIG. 7, a schematic diagramillustrating a high-power radio frequency amplifier 18 coupled to awaveguide 110 with an integrated measurement system 160 that includes areflectometer 164 in accordance with various aspects described herein isshown. The integrated measurement system 160 includes probe antennas 162coupled to a reflectometer 164. The probe antennas 162 include portionslocated within the waveguide 110 that convert radio frequencyelectromagnetic waves within the waveguide 110 into an analog electricpower signal. The probe antennas 162 can be any type of antenna usefulfor measuring radio frequency electromagnetic waves within a waveguide,including but not limited to, dipole antennas.

The reflectometer 164 can include any components useful for measuringthe phase of a radio frequency signal including, but not limited to, adirectional coupler containing matched calibrated detectors or a pair ofsingle-detector couplers oriented so as to measure the electrical powerflowing in both directions within the waveguide 110. In this way, theintegrated measurement system 160 can characterize the radio frequencytransmissions according to power and phase and can be used to form anetworked description as embodied in the scattering matrix orS-parameters. In one non-limiting implementation, the reflectometer 164is a six port reflectometer configured to measure the phase of theforward and backward radio frequency radiation within the waveguide.

The reflectometer 164 is coupled to the probe antennas 162 and caninclude an analog-to-digital convertor (ADC) such that the output signalindicative of the phase or power of the radio frequency electromagneticwave within the waveguide 110 or scattering matrix is digital andreadily input to a device such as the RF signal generator (cf. element16 in FIG. 1), controller (cf. element 14 in FIG. 1) or the RFcontroller (cf. element 32 in FIG. 1).

The electromagnetic cooking device 10 may utilize one or more controlmethods to adjust the power level to reach a desired set-point level.Such a process may have challenges that are not easily resolved byconventional control schemes. For example, in order to minimize cooktime, the device 10 may attempt to reach a maximum power level orset-point level as fast as possible. However, if the maximum power levelis overshot, the high-power amplifiers 18A-D may be damaged. For thisreason, the system may implement a control scheme that preventsover-damping that could extend cooking time, while also protecting thecircuitry and hardware from exceeding a maximum power level.

Referring to FIG. 8, a flow chart of a method 600 for control of theoutput power level of the device 10 is shown. In some embodiments, anamplitude of the power utilized to generate the RF feeds 26A-D, 226 A-Dmay generally be controlled by the controller 14 in communication withthe power supply 12 and/or the amplitude generator 38. Additionally, thecontroller 14 may be operable to detect the power level output from eachof the high-power amplifiers 18A-D via the measurement system (e.g.integrated measurement system 150, 160). Accordingly, upon initiation ofa heating process in step 602, the controller 14 may set the outputpower level P_(O) of one or more of the high-power amplifiers 18A-D to adesired or target output power P_(T). Additionally the controller 14 maymonitor the measured power P_(x). In step 604, the controller 14 mayalso control or update the phase shift between or among the RF feeds18A-D by controlling the RF controller 32. Throughout the method 600,the controller 14 may receive signals communicating the measured powerP_(x) from the measurement system. In this way, the device 10 mayprovide for closed loop feedback to ensure that the target output powerP_(T) is rapidly achieved and maintained.

As previously discussed the high-power amplifiers 18A-D may be damagedif the power level exceeds a maximum power level P_(max) or rated powerlevel. Accordingly in step 606, the controller 14 may compare themeasured power P_(x) to the maximum power level P_(max). If the maximumpower level P_(max) is exceeded, the controller 14 may continue to step608 and decrease the setting for the output power P_(O) by the maximumpower adjustment P_(max) _(_) _(decrease). The maximum power adjustmentmay be one of a plurality of power adjustment levels that may be appliedby the controller 14 to adjust the output power P_(O) from thehigh-power amplifiers 18A-D. Additional power adjustment levels and therelationship among the power adjustment levels are further discussed inthe following description. The controller may adjust the output powerP_(O) by controlling the power supply 12 and/or the amplitude generator38.

In step 606, if the measured power level P_(x) is less than the maximumpower level P_(max), the method may continue to step 610 to set orupdate the target power P_(T). In step 612, the controller 14 maycompare the measured power level P_(x) to the target power P_(T) todetermine the power difference ΔP. Continuing to step 614, thecontroller 14 may determine whether the power difference ΔP is negativeor positive and accordingly, whether the output power P_(O) needs to beincreased or decreased respectively. If the power difference ΔP isgreater than zero, the controller 14 may compare the power difference ΔPto a plurality of adjustment thresholds and decrease the output powerP_(O) by a power adjustment level in steps 616 to 624. If the powerdifference ΔP is less than zero, the controller 14 may compare the powerdifference ΔP to a plurality of adjustment thresholds and increase theoutput power P_(O) by a power adjustment level in steps 626 to 634. Inthis way, the device 10 may compensate for differences between themeasured power level P_(x) and the target power P_(T) efficientlywithout requiring significant processing power from the controller 14.

If the power difference ΔP is greater than zero in step 614, thecontroller 14 may continue to step 616 to compare the absolute value ofthe power difference |ΔP| to a low power decrease threshold. In step618, if the power difference |ΔP| is less than the low power decreasethreshold, the controller 14 may maintain the output power level P_(O)at a current setting. If the power difference |ΔP| is greater than thelow power decrease threshold, the controller 14 may continue to step 620to compare the power difference |ΔP| to a high decrease threshold. Instep 620, if the power difference |ΔP| is greater than the high powerdecrease threshold, the controller 14 may continue to step 622 todecrease the output power level P_(O) by a fast decrease poweradjustment level P_(fast) _(_) _(decrease). In step 620, if the powerdifference |ΔP| is less than the high power decrease threshold, thecontroller 14 may continue to step 624 to decrease the output powerlevel P_(O) by a slow decrease power adjustment level P_(slow) _(_)_(decrease). The fast decrease power adjustment level P_(fast) _(_)_(decrease) may be greater in magnitude than the slow decrease poweradjustment level P_(slow) _(_) _(decrease). In this way, the controller14 may cause the output power level P_(O) to change rapidly or slowly toprovide a desired system response of the device 10. Following any ofsteps 618, 622, or 624, the controller 14 may return to step 602.

If the power difference ΔP is less than zero in step 614, the controller14 may continue to step 626 to compare the absolute value of the powerdifference |ΔP| to a low power increase threshold. In step 628, if thepower difference |ΔP| is less than the low power increase threshold, thecontroller 14 may maintain the output power level P_(O) at a currentsetting. If the power difference |ΔP| is greater than the low powerincrease threshold, the controller 14 may continue to step 630 tocompare the power difference |ΔP| to a high increase threshold. In step630, if the power difference |ΔP| is greater than the high powerincrease threshold, the controller 14 may continue to step 632 toincrease the output power level P_(O) by a fast increase poweradjustment level P_(fast) _(_) _(increase). In step 630, if the powerdifference |ΔP| is less than the high power increase threshold, thecontroller 14 may continue to step 634 to increase the output powerlevel P_(O) by a slow increase power adjustment level P_(slow) _(_)_(increase). The fast increase power adjustment level P_(fast) _(_)_(increase) may be greater in magnitude than the slow increase poweradjustment level P_(slow) _(_) _(increase). In this way, the controller14 may cause the output power level P_(O) to change rapidly or slowly toprovide a desired system response of the device 10. Following any ofsteps 628, 632, or 634, the controller 14 may return to step 602.

As discussed herein, the method 600 may provide for the output powerlevel P_(O) to be adjusted by the plurality of power adjustment levels.The different power adjustment levels may provide for the output powerlevel P_(O) to be adjusted by a magnitude commensurate to a specificstate of the output power level P_(O) in comparison to the target powerlevel P_(T) and the maximum power level P_(max). For example, arelationship among the power adjustment levels discussed herein may beas follows: P_(max) _(_) _(decrease)>P_(fast) _(_) _(increase)>P_(slow)_(_) _(increase) and P_(max) _(_) _(decrease)>P_(fast) _(_)_(decrease)>P_(slow) _(_) _(decrease). Additionally, the high increaseand high decrease thresholds may correspond to greater values than thelow increase and low decrease thresholds. Accordingly, each of theplurality of power adjustment levels and the power level thresholdsdiscussed herein may be adjusted to suit a variety of applications toprovide a desired response of the device 10.

By characterizing the conveyed radio frequency transmissions accordingto power and phase measurements or scattering matrix, theelectromagnetic cooking device (cf. element 10 in FIG. 1) withsolid-state radio frequency sources can precisely excite an enclosedcavity (cf. element 20 in FIG. 1) by controlling the coupling factor ofthe resonant modes or standing waves that determine the heating patterntherein. That is, a solid-state electromagnetic cooking device canenergize desired heating patterns by coupling specific resonant modes tothe microwave cavity via the actuation of the radio frequency sourceswhere the heating pattern is determined by the modulus of the resonantmode. The resonant modes are a function of the cavity dimension, foodload type, food load placement and excitation condition of the multiplecoherent radio frequency sources (e.g. the operating frequency and phaseshift between the sources, etc.). The electromagnetic cooking device canbe configured to control the solid-state radio frequency sources toselect the coupling factor of the resonant modes to energize a specificheating pattern or a sequence of heating patterns over time. The heatingpatterns related to specific resonant modes can determine the evennessor unevenness of the cooking process. However, because the resonantmodes are a function of the food load type and placement, the cavitysize and excitation condition, it is not possible to have an a prioriknowledge of the resonant modes and their critical frequencies.

Therefore, the electromagnetic cooking device can be configured todetermine the resonant modes within an enclosed cavity in-situ.Referring now to FIG. 9, a schematic diagram illustrating a resonantcavity 222 coupled to two RF feeds 226A,B embodied as waveguides inaccordance with various aspects described herein is shown. The RF feeds226A,B transfer power from their respective high-power amplifiers (cf.elements 18A,B in FIG. 1) to the enclosed cavity 222. The RF feeds226A,B can be coupled to the enclosed cavity 222 in spatially separatedbut fixed physical locations. The RF feeds 226A,B can convey RFtransmissions to the enclosed cavity 222 at a selected frequency andphase where the phase shift or difference between the RF transmissionsdirectly relates to the class of symmetry of the excited resonant mode.For example activating the RF sources in an in-phase relationship (i.e.phase shift=0°) activates modes of even symmetry while activating thesources in an antiphase relationship (i.e. phase shift=) 180° activatesmodes of odd symmetry. The symmetries determine the heating patterns inthe oven as will be described below. Although the example is given thatactivating the RF sources in an in-phase relationship (i.e. phaseshift=0°) activates modes of even symmetry while activating the sourcesin an antiphase relationship (i.e. phase shift=) 180° activates modes ofodd symmetry, other phase shifts may be employed depending on thehardware architecture of the system.

In operation, the electromagnetic cooking device determines the set ofsymmetries (e.g. even or odd) for the resonant modes to be excitedwithin the cavity 222. The electromagnetic cooking device is configuredto excite the cavity 222 for a set of operating frequencies and storethe efficiency measured for each frequency. The efficiency is determinedby the useful power output divided by the total electrical powerconsumed which can be measured according to the ratio of forward powerless the backward power to forward power as in:

$\eta = \frac{{\sum P_{forward}} - {\sum P_{backward}}}{\sum P_{forward}}$

The electromagnetic cooking device is configured to store the efficiencymap in memory for the excited classes of symmetries.

Referring now to FIG. 10, a graphical diagram illustrating efficiencyversus frequency for in-phase excitations 228 and antiphase excitations230 of the resonant cavity is shown. In this non-limiting illustrativeexample, the electromagnetic cooking device is configured to conduct twosets of excitations for each operating frequency and obtain twoefficiency measurements.

Referring now to FIG. 11, a diagram illustrating features of a method ofanalysis to determine the resonant modes of the cavity in accordancewith various aspects described herein is shown. The electromagneticcooking device can analyze the recorded map of efficiency (shown for thein-phase excitation 228) by modeling the response as a passband RLCcircuit in order to recognize the critical frequencies of the poles(i.e. the resonant frequencies of the resonant modes) that have beenexcited for the specific class of symmetry. For this purpose, aprocessor 250 as a physical or logical subcomponent of the controller(cf. element 14 in FIG. 1) or the RF controller (cf. element 32 in FIG.2) can be configured to identify local maxima of the efficiencyfunction. The processor 250 can implement any algorithm useful fordetermining the critical frequencies of the poles of the efficiency mapincluding, but not limited to vector fitting, magnitude vector fitting,etc. In this way, the processor 250 can determine a list of resonantfrequencies 252 for each symmetry plane.

Additionally, the processor 250 can determine a quality factor(Q-factor) based on the relative bandwidth of each determined pole. Theprocessor 250 can determine the presence of foodstuff located within thecavity based on the estimate of the Q-factor. For example, if theprocessor 250 determines that a selected resonant mode has a lowQ-factor such as at or below seven, the processor 250 can determine thatthe portions of the enclosed cavity where the excited mode has a localor global maximum contain foodstuff. Similarly, if the processor 250determines that a selected resonant mode has a high Q-factor such asgreater than 1000, the processor can determine that the portions of theenclosed cavity where the excited mode has a local or global maximum donot have foodstuff. The processor 250 can classify the type of foodstufflocated within the cavity based on the estimate of the Q-factor. Forexample, frozen food has a Q-factor of about 300, water has a Q-factorof about 7 and metal objects have a Q-factor of about 1000. For eachdetermined pole, the processor 250 can associate a resonant frequencyused to excite the mode and a Q-factor for determining the type offoodstuff that will be heated by the mode. Additional benefits ofdetermining the Q-factor are described below.

Referring now to FIG. 12, a diagram illustrating features of a method tocharacterize the resonant modes of the cavity in accordance with variousaspects described herein is shown. Building on the previously describedexample of an in-phase excitation 228 of the radio frequency feeds226A,B where a processor of the electromagnetic cooking devicedetermines a set of poles 252 indicative of the resonant modes excitablein the cavity 222, the determined poles 252A-C each correspond to aheating pattern 260A-C within the cavity 222. Recall that the heatingpattern is determined by the modulus of the resonant mode. Each heatingpattern 260A-C will have a spatial pattern with contours indicative ofuniform heating. While depicted in FIG. 12 with a binary set ofcontours, the actual heating patterns will include many contoursindicative of a continuum of heating levels. For ease of understanding,the single contour level indicates the hottest areas of the heatingpattern and demonstrates the even and odd symmetries of the resonantmodes.

Referring now to FIGS. 13A and 13B, a schematic diagram illustratingfeatures of a method to locate and classify foodstuff 300A,B positionedwithin a resonant cavity 222 in accordance with various aspectsdescribed herein is shown. Initiating an antiphase phase excitation(shown in FIG. 13A), the electromagnetic cooking device can generate aheating pattern 360A in the cavity 222 with an even symmetry where themaximum heating contours 302 do not occur in the center of the cavity222. Because a large portion 312 of the foodstuff 300A is lying within aminimum of the heating pattern 360A and only a small portion 310 of thefoodstuff 300A is lying within a maximum of the heating pattern 360A,the cavity reflections are more significant than the electromagneticresponse from the foodstuff 300A leading to a relatively low efficiency.In contrast, because a large portion 314 of the foodstuff 300B is lyingwithin a maximum of the heating pattern 360B and only a small portion316 of the foodstuff 300B is lying within a minimum of the heatingpattern 360B for an in-phase excitation (FIG. 13B), the cavityreflections are minimized and the efficiency is higher than theefficiency determined during the even symmetry excitation. Therefore,the electromagnetic cooking device can determine if foodstuff is locatedin the center of the cavity 222 by comparing the efficiencies betweenthe efficiencies between an in-phase excitation and an antiphaseexcitation. To wit, a higher efficiency with in-phase excitationindicates that foodstuff is not located in the center of the cavity 222and a higher efficiency with an antiphase excitation indicates thefoodstuff is located at the center of the cavity 222. In this way, theelectromagnetic cooking device can be configured to determine thepresence of foodstuff positioned in the center of the microwave cavity222 based on the efficiency of the activated resonant modes of evensymmetry or determine the presence of foodstuff positioned remotely fromthe center of the microwave cavity 222 based on the efficiency of theactivated resonant modes of odd symmetry.

Additionally, the processor can be configured to further analyze theQ-factors according to the efficiency and symmetry of the resonant modesto detect and locate more than one type of foodstuff in the cavity 222.The processor can be configured to average the Q-factors for a subset ofthe identified resonant modes to classify a portion 310, 314 of afoodstuff 300A, 300B according to its position within the microwavecavity 222. For example, the processor can average the Q-factors of theeven symmetry modes to determine the type of foodstuff located in aportion 310 of the foodstuff 300A that intersects with the maximumheating contours 302 of the even symmetry heating patterns 360A.Similarly, the processor can average the Q-factors of the odd symmetrymodes to determine the type of foodstuff located in a portion 314 of thefoodstuff 300B that intersects with the maximum heating contours 304 ofthe odd symmetry heating patterns 3606.

Cooking applications usually require power levels in the range ofhundreds of watts, as a very common power budget for magnetron heatingsources in microwave ovens is in the range of 800-1000 W. Nonetheless,not all applications require such a high power level. For example, anapplication may require a lower power level as low as 80 W to ensurehomogeneous heating and/or a controlled process. Moreover, some cookingprocesses are destroyed or harmed if too high power levels are used(i.e. the quality of the cooking process diminishes as power levelincreases). One example of such a process is melting of butter orchocolate. Another example is raising bread, where a temperaturesuitable for yeast growth must not be exceeded for a certain amount oftime.

The use of solid-state sources allows a precise excitation of theenclosed cavity 20, 222, i.e. precise coupling to certain resonant modesto which specific heating patterns correspond. As noted above, theresonant modes are a function of the cavity dimension, food load typeand displacement and excitation condition (i.e. operating frequency andphase shift between sources in case of use of multiple coherentsources). On the other hand, with traditional non-coherent magnetronsources, such coupling is less controllable since the operatingfrequency is fixed and the phase shift relationship does not exist. Inorder to leverage the increased controllability of solid-state sourcesit is desirable to control the coupling factor of the resonant modes inorder to realize a specific heating pattern and/or a specific sequenceover time of heating patterns related to specific resonant modes inorder to achieve increased evenness and/or controlled unevenness. Suchcontrolled unevenness may be used for a zone cooking application inwhich the electric field, namely the source of heating pattern, isunbalanced to the left or to another portion of the enclosed cavity 20,222. Because the resonant modes are a function of the food load and itsdisplacement, cavity size, and excitation condition, it is not possibleto have an a priori knowledge of the resonant modes and their criticalfrequencies. It is therefore not possible to determine which resonantmodes are excited for a specific set of cavity size/food load type anddisplacement and excitation condition without having all thisinformation, for example, receiving user input at the user interface 28or having additional sensors like cameras to detect the enclosed cavity20 loading conditions and all its characteristics. Again, thisinformation is needed to have information about the heating pattern anduse it accordingly.

The embodiments described here relate to a method to use preclassifiedresonant modes to be activated (i.e. to which the sources transferenergy) into the enclosed cavity 20, 222 to obtain even or unevenheating of a food load. This technique may be referred to asspectromodal control as it is founded on the connection betweenabsorption spectrum and resonant modes. The theory ensures homogeneousheating patterns, center-dominating heating patterns, or unbalancedpatterns. The theory stems from the observation that in an enclosedcavity 20, 222, the coupling between sources and resonant modes is afunction of the operating frequency, since such resonant modes existonly at specific discrete frequencies (the resonant frequency, criticalfrequency or so-called eigenvalues of the modes). Microwave cavities canbe represented as circuits finding an equivalent circuit that shares thesame frequency response. In view of this circuital (filter-like)representation, the resonant modes may be represented as pass-bandfilters centered at their critical frequencies and with a band inverselyproportional to their Q-factor. The Q-factor is related to the losses(dielectric losses that occur into the load as well as metallic lossescoming from surface currents arising into metals). The passbandrepresentation of the enclosed cavity 20, 222 is depicted in FIG. 14.The coupling of such resonant modes with respect to the operatingfrequency can be thought of as a coupling factor related to thefrequency/time factor of the excitations.

The coupling of the sources with the modes of the resonant enclosedcavity 20, 222 is a function of the excitations displacement and phaserelationship in between them (when multiple coherent sources are used)with respect to the enclosed cavity 20, 222. This second coupling factorcan be thought as related to the ‘space’ factor of the excitations. Theapplied phase shift directly relates to the class of symmetry of thetransferred resonant mode. Take as example the enclosed cavity 222depicted in FIG. 9. Activating the sources in phase relationshipactivates modes of even symmetry while activating the sources inantiphase relationship activates modes of odd symmetry. This behavior isdepicted in FIGS. 13A and 13B where FIG. 13A represents the antiphaserelationship and FIG. 13B represents the in-phase relationship. Theexplanation can be found considering the phase relationship between thetwo planes on which the two sources lay, i.e. the natural phase shiftthat the two aforementioned classes of symmetries impose on the enclosedcavity 222. For instance, every resonant mode (that composes the socalled free-response of the enclosed cavity 20) imposes specificboundary conditions on cavity walls, namely where the sources areplaced. If the enclosed cavity 20, 222 excitation is obtained throughwaveguides, a very common case for microwave ovens 10, the waveguidesshall be placed in the location and with a phase shift in between themthat matches the resonant mode that they are designed to excite. In thiscase, the enclosed cavity 20, 222, when excited (the so calledforced-response), will present an electromagnetic field configurationcorresponding to that which the resonant mode to which the excitation istargeted would have. Using such considerations, it is possible to get amap of critical frequencies and class of symmetries (spectromodalidentification). Moreover, it is possible to measure or estimate thecoupled efficiency for each identified resonant mode.

FIG. 15 is provided to show an example of an unbalanced excitation inthe enclosed cavity 222 and the resulting heating pattern. FIG. 16 isprovided to show an example of a balanced excitation in the enclosedcavity 222 and the resulting heating pattern.

Below is a list that shows the resonant modes classified according totheir symmetry and provided with their critical frequencies andefficiencies. The values shown are for purposes of example.

Symmetry 1 (Even, Average Efficiency=79%)

-   -   Mode 1 (frequency=2.40 GHz, efficiency=70%)    -   Mode 2 (frequency=2.41 GHz, efficiency=95%)    -   Mode 3 (frequency=2.45 GHz, efficiency=80%)    -   Mode 4 (frequency=2.50 GHz, efficiency=72%)

Symmetry 2 (Odd, Average Efficiency=79%)

-   -   Mode 1 (frequency=2.40 GHz, efficiency=69%)    -   Mode 2 (frequency=2.41 GHz, efficiency=78%)    -   Mode 3 (frequency=2.45 GHz, efficiency=90%)

The controller 14 may be configured to perform a method (400) ofactivating a sequence of preclassified resonant modes into an enclosedcavity 20, 222 to control a heating pattern therein with RF radiationfrom a plurality of RF feeds 26A-26D, 226A-226B shown in FIG. 17. Theplurality of RF feeds 26A-26D, 226A-226B transfer the RF radiation intothe enclosed cavity 20, 222 and measure the forward and backward powerat the plurality of RF feeds 26A-26D, 226A-226B. The method includes thesteps of selecting a heating target corresponding to an amount of energythat is to be to delivered to each symmetry plane in the enclosed cavity20, 222 based in part upon a load positioned in the enclosed cavity 20,222 (step 402); detecting asymmetries and find the optimal rotationplane (step 404); generating a heating strategy based on the heatingtarget to determine desired heating patterns, the heating strategyhaving a selected sequence of resonant modes to be excited in theenclosed cavity 20, 222 that correspond to the desired heating patterns(step 406); exciting the enclosed cavity 20, 222 with a selected set ofphasors for a set of frequencies corresponding to each resonant mode ofthe selected sequence of resonant modes (step 408) to create heatingpatterns; and monitoring the created heating patterns based on theforward and backward power measurements at the RF feeds 26A-26D,226A-226B to use closed-loop regulation to selectively modify thesequence of resonant modes into the enclosed cavity 20, 222 based on thedesired heating patterns and the created heating patterns as monitored(step 410).

A heating target is an energy set point specified according to asymmetry plane in the enclosed cavity 20, 222. In other words, a heatingtarget is the amount of energy that the microwave oven 10 is configuredto deliver to each symmetry plane. Moreover, the target set point can bespecified according to the ratio between the symmetry planes. Forexample, the target set point can be set as a 2:1 ratio for even and oddsymmetry planes where the even symmetry plane is set to receive twicethe energy as the odd symmetry plane. The heating target is configuredaccording to food load and cooking cycle requirements. For example, abalanced heating target may be configured for a reheat cycle. In anotherexample, where two separate food loads like two small glasses are placedin a symmetric fashion with respect to the cavity center on left andright halves of the oven 10, the heating target can be configured for aneven symmetry heating pattern.

The spectromodal theory ensures that sources in phase and in anti-phasegive rise to specific heating patterns that are symmetric with respectto the center of the cavity 20, 222. Thus, these patterns are suitablefor managing centered food loads, but may be very susceptible todisplacements, as highlighted in FIG. 18 where most of the energy isinjected in the right side of the food load because of the overlappingof the two patterns.

The point is that a non-centered food load introduces a rotation in thesymmetry plane that causes the system oven-load to lose its symmetricproperties. It is thus possible to compensate for this undesiredscenario, identifying the rotation of the actual symmetry plane andapplying it to the RF feeds 26A-26D, 226A-226B, hence changing theirphase relationship, as depicted in FIG. 19 where α and β are thedelta-phase between the RF feeds 26A-26D, 226A-226B.

This approach can be exploited to manage 3D displacements, i.e. on thewidth axis (as already described in FIG. 18), on the height axis and thedepth axis, by just applying the RF feeds phase-shift to the propersymmetry plane.

The outcome of selecting a heating target in step 402 is a set offrequency-phase shift excitations for each RF feed 26A-26D, 226A-226Bthat couple with one specific resonant mode. The phase-shifts appliedare the ones specific of each symmetry class, i.e. the natural phaseshift that the classes of symmetries impose on the cavity 20, 222. Theseresonant modes might then be called ‘unrotated’ or ‘nominal’ resonantmodes. The manner of identifying asymmetries and finding the optimalrotation plane (step 404) is described below.

The unrotated resonant modes selected refer to a symmetric idealscenario, hence they might be suboptimal for an asymmetric scenario.Such an asymmetrical scenario may be caused by the position of the foodload, or by the system itself (e.g., asymmetries in the manner in whichthe RF excitations are fed into the cavity). After identifying theunrotated resonant modes, the controller 14 checks whether they suit theactual system in order to find the optimal rotation that compensates foreventual asymmetries and thus provides optimized resonant modes. In somecases some of the unrotated resonant modes may turn out to not requirerotation for efficiency optimization. Accordingly, not all optimizedresonant modes are rotated. Step 402 is made up of different substeps:(1) phasors excitations; (2) excitations analysis; (3) resonant moderotation; and (4) use of power and phase sensors (vector) instead ofpower sensors (scalar).

For the first substep (phasors excitations substep (1)), after havingselected a nominal phasor, it is possible to identify a set ofexcitations for each resonant mode to be analyzed, by acting on thephase-shifts and keeping the frequency locked for that resonant mode.Specifically, for each unrotated resonant mode, the controller 14generates a set of excitations with the same frequency (of the nominalmode) and a combination of phase-shifts. The set of phases might bedefined a-priori, statically defined on run-time, or even be adaptiveaccording to different parameters. Furthermore, the phase-axis mightinclude all the phase-shifts inside the analysis range or a few samplesonly, in order to save computational time at the expense ofapproximation. The phase-shifts are not arbitrarily defined, since anexcitation related to a specific symmetry plane might couple withanother one if rotated too close to it. It is thus advantageous for thecontroller 14 to set proper bounds to the phase-axis.

The selected actuations may be stored together with their efficiencies,which can be calculated as:

Efficiency=(sum of input power−sum of reflected power)/(sum of inputpower).

For each mode of each symmetry class, the map phasor/efficiency isstored, i.e. if a cavity has two ports with two possible classes and twomodes for each one has been selected, four sets of excitations will beperformed, each set with all the defined phase-shifts, thus obtainingfour sets of efficiency measurements to be further analyzed. A visualexample is shown in FIG. 20 where for each resonant mode, the controller14 performs the following:

for symmetry 1 the phasors ψ are abs(ψ)=1, arg(ψ)=êjf0−ϕ with ϕ={−67.5°,−22.5°, 0°, 22.5°, 67.5° } for both ports; and

for symmetry 2 the phasors ψ are abs(ψ)=1, arg(ψ)=êjf0−ϕ with ϕ={−67.5°,−22.5°, 0°, 22.5°, 67.5° } for port 1 and ϕ=−180°−{−67.5°, −22.5°, 0°,22.5°, 67.5° } for port 2.

The recorded map of efficiency is then analyzed in the second substep(excitations analysis substep (2)) in order to find the phase-shift thatoptimizes efficiency, since theoretically the efficiency vs phase curveshould follow a sinusoidal trend with a maximum on the actual symmetryplane of the system (which is 0° for symmetric ones).

Different strategies might be adopted in order to draw the efficiency vsphase curve, depending on the choices made at the previous stage. If allthe phase-axis has been considered, it is enough to scan the excitationsand find the one with the highest efficiency. Otherwise it is possibleto apply an interpolation algorithm (linear, spline etc.) or even todefine a model exploiting the a-priori knowledge about the trend of thecurve (LSQ, linear regression etc.). A visual example is shown in FIG.21.

It is also worth noticing that, since the rotation of the axis is thecombination of the phase-shifts between each pair of RF feeds 26A-26D,226A-226B and thus locking one source/source phase relationship to avalue has an impact on all the other relationships, the maximumdetection on one phase direction is correlated to all of the others.Hence, the optimal combination of the phase-shifts is not equal to thecombination of the optimum for each direction taken separately.

This leads to an optimization problem of a (nport−1)-dimensionalfunction, so for a 4-port microwave oven 10 the maximum has to besearched in a 3-dimensional plane.

For instance, given a 4-port microwave oven 10 and a phase-axis to bescanned made of four elements[−pi/4 −pi/8 +pi/8 +pi/4] all the possiblecombinations of the phase-shifts between the ports is (provided that oneis taken as reference, so the phase does not change):

(nport−1)^(nphi)=3⁴=81

Hence, while in a 2-port microwave oven 10 there is only oneefficiency-phase curve to study, in a more complex system the number ofexcitations and sensing needed to find the actual optimum rotation mightdramatically increase.

For example, for a three-port system:

$\begin{matrix}{{Sx} = y} \\{{\begin{bmatrix}{s\; 11} & {s\; 12} & {s\; 22} \\{s\; 21} & {s\; 22} & {s\; 23} \\{s\; 31} & {s\; 32} & {s\; 33}\end{bmatrix}\begin{bmatrix}{x\; 1} \\{x\; 2} \\{x\; 3}\end{bmatrix}} = \begin{bmatrix}{y\; 1} \\{y\; 2} \\{y\; 3}\end{bmatrix}} \\{{{p\left( {y\; 1} \right)} \sim {{y\; 1} \star {y\; 1^{*}}}} =} \\{\left\lbrack {s\; 11 \times 1} \right\rbrack^{2} + \left\lbrack {s\; 12 \times 2} \right\rbrack^{2} + \left\lbrack {s\; 13 \times 3} \right\rbrack^{2} +} \\{{2\left\lbrack {s\; 11\mspace{11mu} s\; 12 \times 1 \times 2} \right\rbrack}\cos \mspace{11mu} {\left( {{\phi \times 1} - {\phi \times 2} - {\phi \; s\; 11} - {\phi \; 12}} \right)++}} \\{{2\left\lbrack {s\; 11\mspace{11mu} s\; 13 \times 1 \times 2} \right\rbrack}\cos \mspace{11mu} {\left( {{\phi \times 1} - {\phi \times 3} - {\phi \; s\; 11} - {\phi \; 13}} \right)++}} \\{{2\left\lbrack {s\; 13\mspace{11mu} s\; 12 \times 2 \times 3} \right\rbrack}\cos \mspace{11mu} \left( {{\phi \times 2} - {\phi \times 3} - {\phi \; s\; 13} - {\phi \; 12}} \right)}\end{matrix}$

The ‘free’ phase shifts in the previous equation (i.e. the quantities tobe controlled) are a number of three while the control variables arejust two. This stems from the fact that the given the phase shiftbetween the first and the second port (φx1-φx2) and the phase shiftbetween the first and the third port (φx1-φx3) the last phase shift(φx2-φx3) is not a control variable but satisfies the previous twoequations. That means that the number of control variables is less thanthe number of variables to be controlled and no optimal control ispossible optimizing one factor at a time.

Different approaches might be used to find the solution, such as:

-   -   solve the full problem;    -   approximate the full problem with a heuristic function;    -   consider all the sub-problems separately and combine the results        (as depicted in the FIG. 21); or    -   consider just one or a subset of the sub-problems (the most        meaningful ones with respect to a specific criterion) and solve        it/them exactly or even approximately.

Once the optimal rotation plane has been found, the resonant mode ischanged accordingly per the third substep (resonant mode rotationsubstep (3)). From reconciling the information from all the symmetryplanes it is possible to have the full picture of the resonant modesavailable in the cavity classified per class of symmetry.

Following substep (3), phase sensors are used to collect the S-matrix ofthe system (scattering matrix) in the fourth substep (use of power andphase sensors substep (4)). The scattering matrix makes it possible toperform the spectromodal excitation without actually exciting thesystem. It is possible instead to apply the equation:

Sx=y

where S is the scattering matrix of the system and x are the inputphasors and y are the output phasors and compute the input and reflectedpowers as:

input power=x*conj(x)

output power=y*conj(y)

where conj denotes the complex conjugate.

As noted above the efficiency can be calculated as:

Efficiency=(sum of input power−sum of reflected power)/(sum of inputpower).

After detecting asymmetries and finding the optimal rotation plane (step404) and thus the optimized resonant modes, the controller 14 generatesa heating strategy (step 406) to utilize the optimized resonant modes.For a given heating strategy, a selected sequence of optimized resonantmodes is stored in memory associated with controller 14. The microwaveoven 10 will be configured to execute the selected sequence by applyingthe proper phase shifts and operating frequencies of the RF channels40A-40D in order to activate the optimized resonant modes present in thelist and couple energy to them in the enclosed cavity 20, 222. Eachoptimized resonant mode can be activated for a specific duration oftime. For example, each mode can be excited for the same time durationor, in another example, each mode can be excited for a duration of timethat is inversely proportional to the experimentally determinedefficiency of the mode. Moreover, the sequence of optimized modes caninclude all the optimized resonant modes or just a subset that isproportional to the heating target ratio. Expanding upon the earlierexample of a target ratio of 2:1, the sequence of optimized modes caninclude twice the number of resonant modes belonging to the firstsymmetry plane with respect to the number of resonant modes belonging tothe second symmetry plane. The resonant modes belonging to a certainsymmetry can be interleaved with resonant modes belonging to the othersymmetry so as not to apply the same heating pattern for too much timethat can detrimentally affect heating performance. In another example,the sequence of optimized modes can be selected such that the sum of theinverse efficiencies of the modes belonging to a first symmetry and thesum of the inverse efficiencies of the modes belonging to a secondsymmetry are selected to satisfy the ratio target energy. In anotherexample, the microwave oven 10 can realize the energy target set pointby regulating the power output used for the RF channels 40A-40D.Collectively, the above described examples represent an open-loopoperation where the heating strategy is set and then applied. An exampleof the open-loop algorithm is depicted in FIG. 22.

The sequence of heating patterns determined in the heating strategy maybe selected in such a way as to perform what is referred to herein as“electronic stirring.” “Electronic stirring” is a sequence of heatingpatterns that results a smooth change in the heating patterns such thatthe spatial correlation between one imposed actuation and the next oneis high. The signal generator 16 may be a small signal generator and beset such that the frequency and phase shifts are smoothly changed overtime in such a way that the heating patterns caused by such excitationsare also smoothly changed. Examples of electronic stirring areillustrated in FIG. 24, which show efficiencies at various phases andfrequency indices. As illustrated by the various lines superimposed inFIG. 24, the sequence of heating patterns follow a number of paths (P)between resonant modes (A and B) identified in the efficiency map. Thus,rather than just alternating excitations between those that produceresonant modes (A and B), various intermediate excitations are generatedlying between the resonant modes (A and B). Although the path (P) islinear in FIG. 24, the path may be stepped, interpolated or followingspecific routes. Such settings may vary based on specific hardwareimplementations and/or variations in a detected resonance map in thefrequency/phase domain. Regardless of the path selected, the controlscheme may attempt to cause a smooth change in the heating pattern bymoving from a first detected resonance (e.g., A) to a second detectedresonance (e.g., B).

Each path in the electronic stirring may be traversed by generatingexcitations with specific frequency and phase shifts. For example, thefrequency and phase of the beginning and ending resonant modes of thepath may be used to identify a sequence of phase and frequency shifts totraverse a path between the two resonant modes. If the path is linearand the excitations are stepped, the phase shifts for each excitationcould be calculated as the difference between the phase of the beginningpoint (first resonant mode) and the phase of the ending point (secondresonant mode) divided by the number of steps or excitations to begenerated between the two modes. Similarly the frequency shifts for eachexcitation could be calculated as the difference between the frequencyof the beginning point (first resonant mode) and the frequency of theending point (second resonant mode) divided by the number of steps orexcitations to be generated between the two modes.

The speed of variations (i.e., the speed of the stirring routes) may bechanged according to the specific food type and/or cooking cycle phase.In addition to specifying the phase and frequency of the controlsignals, the controller 14 may further control a rate of change of thefrequency and phase of the control signals as the path (P) is traversed.In this way, the rate of change or rate of travel along the path (P) maybe utilized to control a stirring speed. Such a speed may vary based ona cooking cycle type and/or type of food load to improve a cookingoperation. For example, the speed of the stirring route may be fasterfor a segment of defrost cycle when a food load is frozen and slowerwhen the food load begins thawing. The manner by which the controller 14may determine that the thawing process has started is described furtherbelow.

By providing such electronic stirring, cooking may be performed moreevenly due to the enhanced heating pattern variety (i.e., simultaneouscoupling to more than one resonance). Moreover, due to the high spatialcorrelation of successive heating patterns due to the specific stirringroute selected and the excitations selected, the edges of the food loadmay be uniformly irradiated. This allows for edge management of thecooking process whereby heated portions of the edges are alternated overtime in order to let portions rest and thermally exchange heat withcooler portions of the food load to avoid burnt edges.

The electronic stirring thus provides a heating strategy that resembleswhat a mechanical solution (i.e., a stirrer or turntable) would provide.This particularly provides enhanced defrosting performance. As discussedherein, a mode may correspond to a frequency and phase of each of the RFsignals and corresponding RF feeds (e.g. the RF feeds 26A-26D,226A-226B). For example, a first RF signal and a second RF signal may begenerated by the RF controller 32 in response to an instruction from thecontroller 14 to activate an RF feed at a mode comprising a frequencyand a phase shift. In response to the instruction, the first RF signalmay be set to operate at the frequency and the phase shift relative to atiming of the second RF signal. Additionally, the second RF signal maybe set to operate at the frequency and the phase shift relative to atiming of the first RF signal. In this way, the controller 14 may inducethe electromagnetic radiation in the cooking cavity 20 to achieve thefrequencies and phases required to provide for the electronic stirringas discussed herein.

More specifically, to perform the electronic stirring discussed above,the controller 14 may be configured to control a scanning operation forthe resonant cavity. The scanning operation may comprise emitting aplurality of frequencies and corresponding phase shifts between or amongthe RF feeds (e.g. the RF feeds 26A-26D, 226A-226B). While emitting theplurality of frequencies, the controller 14 may measure the efficiencyof the reflection power in the cooking cavity 20. As further discussedin reference to FIG. 28, the controller 14 may be operable to map and/orinterpolate the entire efficiency response of the cooking cavity 20 inthe frequency and phase domain.

Based on the measure or interpolated efficiency results, the controller14 may detect a plurality of resonance frequencies for the cookingcavity 20 with a particular food load. The resonant modes may correspondto critical or resonance frequencies of the cooking cavity 20. Forexample, the resonance frequencies of the RF feeds may correspond to afirst resonant mode comprising a first phase and a first frequency, anda second resonant mode comprising a second phase of a second frequency.The controller 14 may select the first resonant mode and the secondresonant mode as waypoints or beginning and end points of the stirringroute. In this way, the controller 14 may be operable to determine apath defining the stirring route as a plurality of intermediate modesbetween the first mode and the second mode.

With the stirring route identified between the first resonant mode andthe second resonant mode, the controller may control an electricstirring procedure by controlling the RF signals supplied to thehigh-power amplifiers 18A-D along the intermediate modes. In order tocontrol the stirring route, the controller 14 may sequentially activatea plurality of high-power amplifiers (e.g. high-power amplifiers 18A-D)to emit the corresponding RF feeds into the cooking cavity along theintermediate modes. In this way, the controller 14 may sequentiallyexcite the cooking cavity 20 at frequencies and phase shifts defined bythe intermediate modes. The controller 14 may adjust the frequencies andphase shifts incrementally in order to smoothly adjust the frequenciesand phase shifts between or among the RF signals to traverse a pathbetween the two resonant modes.

The controller 14 may further adjust a rate of change from oneintermediate mode to the next in order to control a stirring rate. Therate of change may be adjusted based on one or more user settings and/orautomated setting for a particular food type or cooking process. Forexample, the controller 14 may control the stirring rate to maintain afrequency and phase setting for the RF feeds to vary at a rate varyingfrom approximately 0.1 seconds to approximately 4 seconds per mode orsimilarly for each frequency and/or phase variation along the stirringpath. For a defrost operation, a stirring rate may be approximately 0.05to 0.5 seconds per mode. For typical food loads during rapid heatingoperations, the stirring rate may be approximately 0.5 to 1 second permode. Finally for some specific foods, a lower stirring rate may beapplied up to 1 to 3 seconds per mode. In a specific example, thestirring rate may be approximately 2 to three second per mode for apotato or mashed potato heating setting.

Referring back to FIG. 17, after the heating strategy is generated instep 406, the controller 14 excites the enclosed cavity 20, 222 with aselected set of phasors for a set of frequencies corresponding to eachof the selected sequence of heating patterns through RF feeds 26A-26D,226A-226B (step 408).

In operation, the controller 14 can implement closed-loop regulation(step 410) by using an integrated amplifier power measurement system 150to detect the energy delivered to the load or a proxy of deliveredenergy such as the efficiency, in order to determine the net powerbalance expressed as the total input power less the total reflectedpower. The energy measurement can be integrated in an accumulatorrelative to the current symmetry plane. At specified intervals of time,the controller 14 uses closed-loop regulation to rebalance the actuationsequence of the excited modes to increase or decrease the number ofactuations for a specific symmetry plane to better achieve the requiredenergy target set point. In another example, the controller 14 can useclosed-loop regulation to adjust the power applied to the enclosedcavity 20, 222 for a specific symmetry plane or a specific mode. Anexample of the closed-loop algorithm is depicted in FIG. 24. Notice inthe example that after the rebalancing, the number of optimized resonantmodes in the first symmetry plane is reduced by one. The controller 14may also monitor the energy (or a proxy) in order to obtain feedbackabout the axis of rotation applied.

FIG. 25A is an efficiency map of one example of a food load in theenclosed cavity where the cooking appliance includes two ports. FIG. 25Bis an efficiency map of one example of a food load in the enclosedcavity where the cooking appliance includes four ports. Thus theseefficiency maps are a frequency/phase representation of two differentstates. In each map, the resonant modes are marked withsquares/triangles with respect to the symmetry plane in which they lie.The cross marker shown in FIG. 25B depicts a resonant mode that thealgorithm has filtered for some reason (for example, because it is tooclose to another one).

FIG. 26A shows an example of an efficiency map in the frequency/phasedomain where the system is mostly symmetrical and most of the resonancesare around 0° (first symmetry plane) and 180° (second symmetry plane).Such resonances would not need to be rotated. In this example, thehighest efficiency (coupling) is obtained using the nominal axis (first:0°, second 180°). FIG. 26B shows an example of an efficiency map in thefrequency/phase domain where the system is asymmetrical and most of theresonances are not around either 0° (first symmetry plane) or 180°(second symmetry plane). Such resonances may be subject to rotation. Inthis example, the highest efficiency (coupling) is obtained applyingspecific rotations to each pole. If the nominal axis (first: 0°, second180°) were used, a lower efficiency would be obtained.

An alternative to the approach described above is discussed below withreference to FIG. 27. Here, the controller 14 may be configured toperform a method (500) of activating a sequence of preclassifiedresonant modes into an enclosed cavity 20, 222 to control a heatingpattern therein with RF radiation from a plurality of RF feeds 26A-26D,226A-226B shown in FIG. 27. The plurality of RF feeds 26A-26D, 226A-226Btransfer the RF radiation into the enclosed cavity 20, 222 and measurethe forward and backward power at the plurality of RF feeds 26A-26D,226A-226B. The method includes the steps of detecting asymmetries andfinding the optimal rotation plane (step 502); selecting a heatingtarget corresponding to an amount of energy that is to be to deliveredto each symmetry plane in the enclosed cavity 20, 222 based in part upona load positioned in the enclosed cavity 20, 222 (step 504); generatinga heating strategy based on the heating target to determine desiredheating patterns, the heating strategy having a selected sequence ofresonant modes to be transferred to the enclosed cavity 20, 222 thatcorrespond to the desired heating patterns (step 506); exciting theenclosed cavity 20, 222 with a selected set of phasors for a set offrequencies corresponding to each resonant mode of the selected sequenceof resonant modes (step 508) to create heating patterns; and monitoringthe created heating patterns based on the forward and backward powermeasurements at the RF feeds 26A-26D, 226A-226B to use closed-loopregulation to selectively modify the sequence of resonant modes into theenclosed cavity 20, 222 based on the desired heating patterns and thecreated heating patterns as monitored (step 510).

In method 500, the steps of detecting asymmetries and finding theoptimal rotation plane (step 502) and selecting a heating target (step504) are performed in a reversed order than in method 400 describedabove with respect to FIG. 17. In addition, the details of these twosteps are different. Specifically, in step 402, the first, second, andthird substeps (phasors excitations substep (1), excitations analysissubstep (2), and resonant mode rotation substep (3)) are now performedin the asymmetry detecting step 502 rather than the heating targetselection step 504. To find optimum rotations, the controller 14generates a preselected set of excitations to find frequenciesrepresenting unrotated resonant modes and then generates excitations ina small region close to those frequencies representing resonant modeswhile shifting the phases and measuring the resulting efficiencies. If aspecific phase at a frequency leads to an increase in efficiency, theoptimized resonant mode is the phase-shifted one, and the rotation isthe phase shift. Thus, in step 502, substep (1), the controller 14 firstexcites the cavity with a plurality of pre-selected frequencies toidentify unrotated resonant modes and then identifies a set ofexcitations for each unrotated resonant mode to be analyzed by acting ona plurality of phase-shifts and keeping the frequency locked for thatresonant mode. Specifically, for each unrotated resonant mode, thecontroller 14 generates a set of excitations with the same frequency (ofthe nominal mode) and a combination of phase-shifts. The set of phasesmight be defined a-priori, statically defined on run-time, or even beadaptive according to different parameters. Furthermore, the phase-axismight include all the phase-shifts inside the analysis range or a fewsamples only, in order to save computational time at the expense ofapproximation. The phase-shifts are not arbitrarily defined, since anexcitation related to a specific symmetry plane might couple withanother one if rotated too close to it. It is thus advantageous for thecontroller 14 to set proper bounds to the phase-axis.

The selected actuations may be stored together with their efficiencies.For each mode of each symmetry class, the map phasor/efficiency isstored, i.e. if a cavity has two ports with two possible classes and twomodes for each one has been selected, four sets of excitations will beperformed, each set with all the defined phase-shifts, thus obtainingfour sets of efficiency measurements to be further analyzed.

The recorded map of efficiency is then analyzed in the second substep(excitations analysis substep (2)) in order to find the phase-shift thatoptimizes efficiency, since theoretically the efficiency vs. phase curveshould follow a sinusoidal trend with a maximum on the actual symmetryplane of the system.

Once the optimal rotation plane has been found, the resonant mode ischanged accordingly per the third substep (resonant mode rotationsubstep (3)). From reconciling the information from all the symmetryplanes it is possible to have the full picture of the resonant modesavailable in the cavity classified per class of symmetry. Additionaldetails of substeps (1)-(3) are described above with respect to FIG. 17.

In step 504, a heating target is then selected corresponding to anamount of energy that is to be to delivered to each symmetry plane inthe enclosed cavity based in part upon the food load positioned in theenclosed cavity where the heating target includes a plurality ofresonant modes that are rotated using the selected rotations in thepreceding step 502. Step 502 thus includes substep (4) of step 402described above. When selecting a heating target, the controller 14 isfurther configured to select the heating target according to food loadand cooking cycle requirements.

Following step 504, the controller 14 performs steps 506-510, whichcorrespond to steps 406-410 of FIG. 17. Insofar as these steps are thesame, the details of steps 506-510 are not provided. Instead, thedescription of steps 406-410 above is incorporated herein by reference.

With reference to FIG. 28, a method 700 of spectromodal identificationof resonant modes within the cooking cavity 20 is now described. Thesystem 10 may map the resonance peaks over a range of frequencies andphase shifts of the output signals. It is important that the results bemeasured for each system 10 and food load because the resonance map mayvary based on changes in the food load and heating cavity 20 throughouta cooking operation. In general, the controller 14 may detect theresonance map by completing a frequency sweep (step 702) wherebyexcitations at various frequencies and predetermined phase shifts areapplied to the cavity 20 according to symmetries that can be excited inthe system 10. During step 702, the output power of the high-poweramplifiers 18A-D shall be reduced to a safe level, (i.e. low enough toensure no damage even when high reflections occur).

Referring to FIGS. 29A and 29B, an embodiment of the cooking cavity 20comprising four waveguide inlet ports (RF feeds 26A-D, 226A-D) is shown.For step 702, the controller 14 may be configured to supply a differentcontrol signal to each of four corresponding amplifiers 18A-D such thatthere may be three phase shifts that may be applied to the radiationemitted from the RF feeds 26A-D, 226A-D. Accordingly, the controller 14may control an excitation symmetry may be applied to measure theresponse of the system 10 to a particular food load. For example, for afour-port system, the phases may be [0, 0, 0]°, [0, 45, 45]°, [0, 90,90]°, [0 180, 180]°, and so on. Optionally, for step 702, the controller14 may test all the phase shift vectors in order to build a detailedresonance map collecting efficiency at every given frequency/phaseshifts point.

Optionally, the controller 14 may also filter the measured efficiency instep 704 over a frequency span given a fixed phase shift with a low-passfilter. Alternatively, the measured efficiency may be filtered over thefrequency span given a fixed phase shift with an adaptive filter. Theadaptive filter may have weights given by a measured imbalance powerdistribution supplied by each of the amplifiers 18A-D. By filtering theresults, peaks in injected power from the amplifiers 18A-D may beremoved. In this way, false peaks that do not correspond to resonancesof the device 10 may be removed from the results. An example of adaptivefiltering is shown in FIG. 30.

In some embodiments, the controller 14 may model the cooking cavity 20including the food load with a numeric or mathematical model as shown instep 706. The model may relate the efficiency of the cooking cavity 20with a food load to the operating frequency of the RF feeds 26A-D,226A-D. For example, for every axis the model may relate the systemefficiency η and per-channel reflections p of the RF feeds 26A-D, 226A-Dto the rotation angle γ (vector of phase shifts between ports). Thisrelationship is represented as Equations 1 and 2.

η(f,γ)=η₁(f)cos(γ)+η₂(f)sin(γ)+η₃(f)  (Equation 1)

ρ(f,γ)=ρ₁(f)cos(γ)ρ₂(f)sin(γ)+ρ₃(f)  (Equation 2)

Equations 1 and 2 may further be represented with a general formdemonstrated in Equation 3.

x(f,γ)=x _(ic1)(f)cos(γ)+x _(ic2)(f)sin(γ)+x _(ic3)(f)  (Equation 3)

Accordingly, the model of the cooking cavity 20 may comprise a pluralityof unknown interpolation parameters. These interpolation parameters maycorrespond to three variables: x_(ic1)(f), x_(ic2)(f), x_(ic3)(f). Sincethere are three parameters per frequency, the minimum number ofefficiencies to be sampled in order to be able to invert the model ofthe cooking cavity 20 is equal to three. For example for a givenfrequency f, the controller 14 may excite the system 10 with phaseshifts equal to [0, 120, 240° ]. These efficiencies may then be measuredby the measurement system to record the three efficiencies (e.g. 85°,70°, 69°) as follows:

85%=η₁(f)cos(0)+η₂(f)sin(0)+η₃(f)

70%=η₁(f)cos(120)+η₂(f)sin(120)+η₃(f)

69%=η₁(f)cos(240)+η₂(f)sin(240)+η₃(f)

In this way, the controller 14 may continue to calculate a plurality ofinterpolation parameters as the coefficients for the numeric model basedon the measured efficiencies as demonstrated in step 708. Accordingly,the interpolation parameters may correspond to: η₁(f), η₂(f), η₃(f).

With the interpolation parameters, the controller 14 may estimateefficiency results comprising additional phase shifts different than thephase shifts utilized to induce the measured efficiencies as shown instep 710. In some embodiments, the controller 14 may utilize the modelof the system to interpolate the full space for all possible phaseshifts over the operating range of the system. That is, the controller14 may model the efficiency response of the system 10 for the cookingcavity 20 for each food load over substantially all operatingfrequencies and phase shifts of the RF feeds 26A-D, 226A-D.

As discussed herein, the disclosed interpolation method may provide forthe controller 14 to measure efficiency responses for just three or fourfrequency and phase modes. With the measured efficiencies, thecontroller 14 may interpolate the results to get efficiency responsesfor all the other phase shifts based on the interpolation coefficientsof the system including those that have not been tested. Theinterpolation coefficients may be stored in memory. In thisconfiguration, the controller 14 may test the response of the reflectedsignals of only a few input signals to deduce the full efficiency of theheating cavity 20 in the frequency/phase domain. Examples of resonancemaps are shown in FIGS. 25 and 26. The resonance maps of FIGS. 25 and 26demonstrate a plurality of resonance peaks in squares and triangles. Thesquares denote peaks with even symmetry and the triangles denote peakswith odd symmetry.

In step 712, the controller 14 may associate the resonances of thesystem 10 to local maxima in the resonance map. As discussed herein, theresonances of the system may correspond to resonant modes demonstratingcritical or resonant frequencies of the system. The controller 14 maystore the modes in memory and in some embodiments, may utilize the phaseshifts and frequencies associated with the modes to control the RF feedssupplied into the cooking cavity 20. In this way, the controller mayidentify and control a distribution of the electromagnetic energy withinthe cooking cavity 20.

In step 714, the resonance maps of the system 10 may be categorizedbased on an odd, even, or combined frequency distributions among thephase shifts. That is, the applied phase shift directly relates to theclass of symmetry of the coupled resonant mode. For example, the phaseshift in FIG. 29A may correspond to an even symmetry. The phase shift inFIG. 29B may demonstrate the sources in antiphase relationship activatesmodes of odd symmetry. Such classification of the resonances may be madeaccording to their absolute phase (i.e., if they are between 90°-270°then classify as secondary symmetry plane, if less than 90° or more than270° classify as first symmetry plane. In this way, the controller 14may monitor the reflected signals from each of the RF feeds 26A-D,226A-D to identify sample data for a resonance map of the heating cavity20.

The method described above with respect to FIG. 28 may be summarized asfollows. The controller 14 may control the RF feeds corresponding to afirst RF signal and a second RF signal. The RF signals may be within anoperating range of system 10 and controlled by the controller 14 at aplurality of phase shifts between the first RF signal and the second RFsignal. Additionally, the controller 14 may control the amplifier 18 toamplify the RF signals in order to generate the RF feeds in the cookingcavity 20. The controller 14 may further measure a plurality ofefficiencies of the reflection signals in the cavity induced by the RFfeeds for the plurality of phase shifts and estimate efficiency resultsfor the frequency response of the cavity 20. The efficiency results maycomprise additional phase shifts estimated for the operating range ofthe cooking device. In this example, the additional phase shifts aredifferent from the plurality of phase shifts utilized to generate the RFfeeds.

In addition to the efficiency, the controller 14 may additionallymonitor the max reflected power signals for each of the RF feeds 26A-D,226A-D to identify a capability of each of the amplifiers 18A-D tosustain operation of each of the modes of operation discussed herein.For example, based on the reflected power signals, the controller 14 mayidentify a maximum reflection of each individual channel of the RF feeds26A-D, 226A-D. In this way, the controller 14 may compare the drivingpower supplied to the amplifiers 18A-D with the maximum reflectionsignal corresponding to each of the amplifiers 18A-D to determine ifeach of the amplifiers 18A-D is operable to maintain operation at adesired frequency and power. Accordingly, the controller 14 may verifythat the operation of the amplifiers 18A-D is preserved to maintain thesystem models of the amplifiers 18A-D throughout operation. Thecontroller 14 may further be configured to estimate the efficiencyresults based on a numeric model comprising a plurality of interpolationparameters. The interpolation parameters are calculated for the numericmodel based on the plurality of efficiencies measured for the reflectionsignals. In some embodiments, the controller may update theinterpolation parameters for the cooking cavity 20 during a cookingprocess. In order to update the interpolation parameters, the controller14 may measure additional efficiencies of the reflection signals andrecalculate the interpolation parameters to account for changes in theefficiency response that may result from heating the food load.

Benefits of the spectromodal identification method described aboveinclude the ability to detect the efficiency response and the resonancemap of the system, better noise rejection when inconsistent powers areapplied to the system (high-power amplifiers 18A-D overshoots, coarseregulation of the power), and reduced sensing-identification timeresulting in higher effective power (due to the reduction of outputpower of the high-power amplifiers 18A-D to a safe level during step702). Optionally, a random access memory may be used to store‘snapshots’ of the system to notify the user, measure or quantifychanges over time of the snapshots. Another options to use techniquessuch vector fitting or other fitting techniques to classify theresonances in terms of Q-factor and resonant (critical) frequency.

When the RF system of the electromagnetic cooking device is stable for agiven RF excitation (at a set frequency and set phase shift for amultiport system), reflected power is constant. Insofar as reflectedpower is inversely related to efficiency, the efficiency also remainsconstant when the RF system is stable for a given excitation. However,if the RF system is unstable, the reflected power and hence theefficiency varies over time in a noisy fashion. The stronger theinstability in the RF system, the bigger the oscillations in thereflected power. Causes of such instability may be changes incharacteristics of the food load as the cooking cycle progresses. Asexplained further below, such changes in characteristics of the foodload may be volumetric. Thus, by monitoring the change of the reflectedpower or efficiency throughout the cooking cycle, changes in the volumeof the food load may be detected. The ability to detect changes in thevolume of a food load or to detect other changes in characteristics ofthe food load, is advantageous in controlling the following specificprocesses: cooking popcorn, heating milk, bringing liquids to boiling,and melting foods such as chocolate or butter. Another advantage is thatthis ability can be used to detect and therefore prevent splattering ofthe food load in the cooking cavity. These specific examples arediscussed further below under separate headings pertaining to eachprocess.

In a multiport system such as that described above with multiple RFfeeds 26A-D, 226A-D, any change in the input phasors (i.e., frequency,amplitude, phase shifts) will affect efficiency. Thus, one cannot simplymonitor numerical values representing the efficiency throughout thecooking cycle to detect changes in characteristics of the food load whenthe heating strategy for that cooking cycle involves changing the inputphasors throughout the cycle as changes in efficiency may be caused bythe change in phasors rather than changes in the food load. Therefore,the time variation of the coefficient of variation of efficiency may beused to isolate changes in efficiency that are caused by changes incharacteristics of the food load as opposed to those caused from changesin the input phasors.

An electromagnetic cooking device 10 may therefore be provided thatincludes the enclosed cavity 20 in which a food load is placed, thecontroller 14, and the plurality of RF feeds 26A-D, 226A-D configured tointroduce electromagnetic radiation into the enclosed cavity to heat upand prepare the food load, the plurality of RF feeds 26A-D, 226A-D areconfigured to allow measurement of forward and backward power at theplurality of RF feeds. The controller 14 may be configured to performthe steps of the method 720 shown in FIG. 31. Specifically, thecontroller 14 may control the system such that it generates RFexcitations at a specified frequency and phase shifts from the pluralityof RF feeds 26A-D, 226A-D (step 722) for a predetermined period of time(e.g., 0.5 to 4.0 seconds) in accordance with a heating strategy asdiscussed above. Next, over the predetermined time period (or throughoutthe duration of the excitation), the controller 14 measures and analyzesthe backward power at the plurality of RF feeds 26A-D, 226A-D tocalculate efficiency (in the manner discussed above) (step 724),determines a coefficient of variation in the efficiency (steps 726 and728), and monitors the coefficient of variation to identify possiblechanges in a characteristic of the food load (step 730). Thedetermination of the coefficient of variation in the efficiency may bemade by determining a mean and standard deviation (std) of theefficiency over the predetermined time period (step 726) and calculatingthe coefficient of variation from the mean and standard deviation (step728). In step 728, the coefficient of variation may be calculated as(std/mean). Next, in step 732, the controller 14 determines if apossible change is identified in a characteristic of the food load basedon changes in the coefficient of variation over the cooking cycle up tothat point in time where such a change reaches some specified threshold(e.g., a specified change in volume). Note that the specified degree ofchange in the food load characteristic needed to satisfy step 732 willvary depending on the type of food load as will be apparent from theexamples described below. If no such change in the food loadcharacteristic is identified, the controller 14 repeats steps 722-732until such time that such a change is identified. Note that in repeatingstep 722 different input phasors may be used in accordance with theheating strategy. Thus, in executing the method 720, the controller 14recomputes the mean and standard deviation and hence the coefficient ofvariation for the duration of each different input phasor excitation. Inthis way, mean and standard deviations are effectively normalized acrossall the different RF excitations and are comparable regardless ofchanges in the efficiency caused by changes in the input phasors.

Once the controller 14 identifies a change is identified in acharacteristic of the food load that reaches the specified threshold(e.g., a specified change in volume) in steps 730 and 732, thecontroller 14 executes step 734 in which it may either stop the cookingcycle or change a cooking control parameter such as the heating strategyincluding amplitude, frequency and/or phase shifts of the input phasors,and continue through steps 722-732 until such time that another changeoccurs that may trigger yet another change in heating strategy or haltthe cooking cycle. Again, the specific action taken in step 734 willdepend on the type of food load and the corresponding cooking cycle andheating strategy for that type of food load.

Because it is the rate of variation over time and not the absolute levelthat is of interest, by calculating the coefficient of variation of theefficiency, the identification of a change in a characteristic of thefood load is insensitive to the relative efficiency level. This allowscomparisons between the different excitations at different amplitudes,frequencies and phase shifts.

As noted above, once the change in the coefficient of variationidentifies a change in a characteristic of the food load to a specifieddegree, the cooking process may be stopped or altered. Optionally, afrequency scan can be repeated to remap the resonant modes.

Although the example is provided herein where the coefficient ofvariation of efficiency is used, other metrics may be used to determinea change in a characteristic of the food load. Such other metrics maymeasure the amount of ‘noise’ superimposed to the efficiency where thenoise can be normalized across all input phasors. Such metrics maydistinguish the kind of variations or system instability. One approachmay be to execute a fast Fourier transform (FFT) on the measuredbackward power or the computed efficiency so as to focus on highfrequency content caused by changes in the food load as changes causedby changes in input phasors present themselves in low frequency contentdue to the changes in input phasors at 0.5 to 4.0 second increments. Itshould be noted that the efficiency is being continuously calculatedthroughout the duration of each separate RF excitation and that thechanges that are being monitored are not in the seconds domain, butrather in the less-than-one-second domain, such that a change in foodload may be detected during any one excitation.

Having now described the manner in which the coefficient of variationcan be computed, several applications are now described.

A. Automatic Boiling Detection

Referring to FIGS. 32A and B, sample data is shown for the efficiency(FIG. 32A) and corresponding coefficient of variation of efficiency(FIG. 32B) for a liquid heated in the cooking cavity 20 over a period oftime. For purposes of illustration, the efficiency and correspondingcoefficient of variation are shown during each of a still phase, a weakboiling state, and a strong boiling state of the liquid. By calculatingthe coefficient of variation of efficiency and monitoring the signalproperties, the controller 14 is operable to detect oscillations in thereflected power that is proportional to the oscillations in the volumeof the liquid. Notably, the coefficient of variation of efficiency isproportional to a boiling level of the liquid. That is, the greater thedegree of boil, the greater the coefficient of variation of efficiency.Based on these properties, the controller 14 may detect a heating stateof the liquid that may include a beginning time of boiling, the weakboiling state, and the strong boiling state.

The controller 14 may control the heating of a liquid by performingheating method 740 shown in FIG. 33, in which the controller 14 firstmeasures the coefficient of variation of efficiency during a still phase(step 742) that may correspond to an initial heating period. Forexample, the still phase may include a predetermined time period asshown in FIG. 32B. The coefficient of variation of efficiency measuredduring the still phase may be utilized to define a threshold (e.g.,threshold 743, FIG. 32B) indicative of the strong boiling state (step744). In some embodiments, the coefficient of variation of efficiencymeasured during the still phase may be stored to memory prior todefining the threshold. Alternatively, the threshold may be defined by apredetermined value stored to memory. For example, the threshold may bedetermined by measuring the mean of the coefficient of variation duringthe still phase or time period therein (e.g., the first 20 seconds) andmultiplying the mean by a constant (e.g., 3). Thus, it will beunderstood that in some embodiments, the threshold may correspond to theproduct between the mean of the coefficient of variation of efficiencymeasured during a time period of the still phase and a predeterminedmultiplier.

Once the threshold is defined, the controller 14 monitors thecoefficient of variation of efficiency (step 746), and if thecoefficient of variation of efficiency is greater than or equal to thethreshold for a predetermined period of time (step 748), it isdetermined that the liquid is in the strong boiling state, and inresponse, the controller 14 adjusts a power level of amplifiers 18A-D(e.g., changing a duty cycle, input power, etc.) (step 750). Otherwise,the controller 14 determines that the liquid is in a weak boiling stateand continues to monitor the coefficient of variation of efficiency(step 746) until the condition specified at step 748 is satisfied. Withrespect to step 750, the adjustment may include maintaining orincreasing the power level to keep the liquid in the strong boilingstate, decreasing the power level to maintain the liquid near the strongboiling state or returning the liquid to the weak boiling state, orstopping the heating of the liquid altogether by deactivating amplifiers18A-D. Furthermore, the adjustment to the power level may be limited toa period of time set by the controller 14. Optionally, once thecondition specified at step 748 is satisfied, or in other words, thecontroller 14 has detected that the liquid has reached the strongboiling state, the controller 14 may output a notification to the userinterface 28 or a mobile device such as a smartphone (step 752). Inresponse, a user may provide input to the controller 14 (via the userinterface 28 or the mobile device) accepting the adjustments describedat step 750 or otherwise making other adjustments, if desired.

The controller 14 may additionally or alternatively control the heatingof the liquid by performing heating method 760 shown in FIG. 34, inwhich the controller 14 first measures the coefficient of variation ofefficiency during the still phase (step 762). The coefficient ofvariation of efficiency measured during the still phase may be utilizedto define a mask (e.g., mask 763, FIG. 32B) indicative of the strongboiling state (step 764). In some embodiments, the coefficient ofvariation of efficiency measured during the still phased may be storedto memory prior to defining the mask. Alternatively, the mask may bedefined by a predetermined function stored to memory. It is contemplatedthat the mask may be expressed as a rising linear, exponential, orlogarithmic function. Once the mask is defined, the controller 14monitors the coefficient of variation of efficiency (step 766), and ifthe coefficient of variation of efficiency fits to the mask for apredetermined period of time (step 768), the controller 14 determinesthat the liquid is in the strong boiling state, and in response, adjustsa power level of amplifiers 18A-D (step 770). Otherwise, the controller14 determines that the liquid is the weak boiling state and continues tomonitor the coefficient of variation of efficiency (step 746) until thecondition specified at step 768 is satisfied. With respect to step 770,the adjustment may include maintaining the power level, increasing thepower level, decreasing the power level, or stopping the heating of theliquid altogether. Optionally, once the condition specified step 768 issatisfied, or in other words, the controller 14 has detected that theliquid has reached the strong boiling state, the controller 14 mayoutput a notification to the user interface 28 or a mobile device suchas a smartphone (step 772). In response, a user may provide input to thecontroller 14 (via the user interface 28 or the mobile device) acceptingthe adjustments made at step 770 or otherwise making other adjustments,if desired.

It will be appreciated that a user may select which method 740, 760 toimplement using the user interface 28 or a mobile device.Advantageously, the methods 740, 760 described above greatly improveenergy consumption and enable a user to obtain an optimum boiling leveland temperature of a liquid without having to input any specificcharacteristics of the liquid such as mass or volume. Likewise, thesystem 10 is able implement the methods 740, 760 without having todetect the specific mass or volume of the liquid.

B. Automatic Milk Heating

Referring to FIG. 35, sample data is shown for the coefficient ofvariation of efficiency (metric output) for a specific liquid, namelymilk, which is heated in the cooking cavity 20 over a period of time.The coefficient of variation results for milk demonstrate changes in thereflected power at approximately 37° C., 50° C., and 85° C. based uponsteep changes in permittivity with respect to temperature rise that arerelated to protein denaturation and other chemical changes. Thesechemical reactions drive frequency shifts and Q-factor variations in theresonances of the system 10. Each of the changes corresponds to a stateof the milk that may be detected by the controller 14 and utilized inconjunction with measured resonance shifts to estimate the temperatureof milk and control an automated heating function. That is, thecontroller 14 may indirectly detect the temperature of the milk andcontrol a heating state of the milk in response to the milk temperaturebeing: below 37° C., between 37° C. and 50° C., between 50° C. and 85°C., and greater than 85° C. In this way, the controller 14 mayautomatically prepare the milk to a specific temperature or range basedon user-specified temperature input. Such a feature is particularlybeneficial for heating milk to the appropriate temperature for a youngchild or baby.

The controller 14 may control the heating of milk by performing method780 shown in FIG. 36, in which the controller 14 first measures thecoefficient of variation of efficiency during a still phase (step 782)that may correspond to an initial heating period. The coefficient ofvariation of efficiency measured during the still phase may be utilizedto define a threshold indicative of a temperature specified by a user(step 784) via the user interface 28 or a mobile device, for example. Insome embodiments, the coefficient of variation of efficiency measuredduring the still phase may be stored to memory prior to defining thethreshold. Once the threshold is defined, the controller 14 monitors thecoefficient of variation of efficiency (step 786) in conjunction withresonance shifts, and if the coefficient of variation of efficiency isgreater than or equal to the threshold (step 788), the controller 14adjusts the power level of amplifiers 18A-D (step 790). In one specificexample, the controller 14 may maintain the milk at the temperaturespecified by the user (e.g., a “keep warm” functionality) or stop theheating of the milk altogether. Optionally, once the condition specifiedat step 788 is satisfied, or in other words, the controller 14 hasestimated that the milk has reached the temperature specified by theuser, the controller 14 may output a notification to the user interface28 and/or a mobile device such as a smartphone (step 792). In response,a user may provide input to the controller 14 (via the user interface 28or the mobile device) accepting the adjustments described at step 790 orotherwise making other adjustments, if desired.

Advantageously, method 780 described above greatly improves energyconsumption and enables a user to obtain an optimum milk temperaturewithout having to input any specific characteristics of the milk such asmass or volume. Likewise, the system 10 is able to implement method 780without having to detect the specific mass or volume of the milk.

C. Automatic Butter and Chocolate Melt

The system 10 may also be utilized to accurately melt butter andchocolate without overheating the melted liquid. The controller 14 maycontrol the melting of a food load such as butter or chocolate byperforming a method 800 shown in FIG. 37, in which the controller 14first scans the cavity 20 to measure resonances using spectromodalidentification and generates a resultant resonance map (step 802), whichmay be stored to memory. In addition, the controller 14 may detect thecoefficient of variation of efficiency during a still phase that maycorrespond to an initial heating period and initial volume (step 804).Next, the controller 14 conditionally repeats the measurement of theresonances after a predetermined period of time and/or when a change inthe coefficient of variation of efficiency is detected (step 806). Forexample, the controller 14 may identify one or more changes in thecoefficient of variation of efficiency following the still phase to be achange in volume of the food load. For chocolate, butter, and similarsubstances, the change in volume corresponds to a change in shape andconsistency at the beginning of melting. The controller 14 may thendetermine if the variation between the resonance maps satisfies athreshold condition that is indicative of a melting condition (i.e., thefood load is melting) (step 808). If not, the controller 14 controls theamplifiers 18A-D to apply power to the cavity 20 (e.g., with apredefined amount of energy) (step 810) before returning to step 806.Otherwise, the controller 14 adjusts the power level of amplifiers 18A-D(step 812) once the threshold condition is satisfied in step 808. In onespecific example, the controller 14 determines that the conditionspecified in step 808 is satisfied if the rate of variation over time ofthe resonances falls below a predetermined threshold. In response, thecontroller 14 stops the heating of the food load. In some embodiments,the controller 14 will stop the heating process once a predefined amountof energy has been applied to the food load. In some control schemes, itis contemplated that the controller 14 may also adjust the power levelof the system 10 according to the state of the food load. Optionally,once the condition specified at step 808 is satisfied, or in otherwords, the controller 14 has detected that the food load has melted, thecontroller 14 may output a notification to the user interface 28 or amobile device such as a smartphone (step 814). In response, a user mayprovide input to the controller 14 (via the user interface 28 or themobile device) accepting the adjustments described at step 812 orotherwise making other adjustments, if desired.

By using method 800 to control the system 10 during a melting process,perfect melting or softening can be automatically achieved with no burntportions. Additionally, a user is not required to input the mass orvolume of the food load to be melted. Furthermore, energy is saved dueto the automatic stopping once melting has been achieved.

D. Automatic Splatter Control for Liquids, Sauces, and Mixed Loads

Referring now to FIG. 38, sample data is shown for the coefficient ofvariation (metric output) of efficiency for a liquid heated in thecooking cavity 20 over a period of time. The liquid may correspond to asauce, for example. In some embodiments, the liquid may be part of amixed load, that is, a food load having both liquid and solidconstituents.

The controller 14 may control the heating of the liquid or an at leastpartially liquidized food load using a method 820 shown in FIG. 39, inwhich the controller 14 first measures the coefficient of variation ofefficiency during a still phase (e.g., starting point, FIG. 38) that maycorrespond to an initial heating period (step 822). The coefficient ofvariation of efficiency for the still phase may be utilized to define athreshold (e.g., threshold 823, FIG. 38) indicative of a boiling state(step 824). In some embodiments, the coefficient of variation ofefficiency measured during the still phased may be stored to memoryprior to defining the threshold. Alternatively, the threshold may bedefined by a predetermined value stored to memory. Once the threshold isdefined, the controller 14 monitors the coefficient of variation ofefficiency (step 826), and if the coefficient of variation of efficiencyis greater than or equal to the threshold (step 828), the controller 14adjusts a power level of amplifiers 18A-D (e.g., changing a duty cycle,input power, etc.) (step 830). Otherwise, the controller 14 continues tomonitor the coefficient of variation of efficiency (step 826) until thecondition specified at step 828 is satisfied. With respect to step 830,the adjustment may include reducing the power level until thecoefficient of variation of efficiency is reduced by a predeterminedamount followed by increasing the power level for a predetermined amountof time or until the coefficient of variation of efficiency satisfiesthe condition specified in step 828 (e.g., reaches the threshold). Inthis manner, the liquid is heated while avoiding splattering. So long asthe condition specified in step 828 is satisfied, steps 828 and 830 maybe continuously repeated or the heating of the liquid may be stoppedafter a predetermined period of time has passed. Optionally, once thecondition specified at step 828 is satisfied, or in other words, thecontroller 14 has detected that the liquid has reached the boilingstate, the controller 14 may output a notification to the user interface28 or a mobile device such as a smartphone (step 832). In response, auser may provide input to the controller 14 (via the user interface 28or the mobile device) accepting the adjustments described at step 830 orotherwise making other adjustments, if desired.

E. Automatic Popcorn Cooking

Referring now to FIG. 40, sample data is shown for the coefficient ofvariation of efficiency (metric output) for popcorn being popped in thecavity 20 over a period of time. From the results, the coefficient ofvariation of efficiency is proportional to the frequency of poppedkernels over time. Additionally, the coefficient of variation ofefficiency is affected by sudden volume increases in the bag of popcornonce the popping begins. Accordingly, by monitoring the coefficient ofvariation of efficiency, the controller 14 may control the popping ofthe popcorn based on a frequency or timing of the kernels popped overtime. The change in the coefficient of variation of efficiency inresponse to the popping may be linked to changes in volume anddistribution of the kernels in the popcorn bag. As will be described ingreater detail below, the controller 14 may control the popping of thepopcorn based on detecting a beginning of popping and a threshold atwhich popping is complete.

The controller 14 may control a popping process of popcorn by using amethod 840 shown in FIG. 41, in which the controller 14 first measuresthe coefficient of variation of efficiency during a still phase (step842) that may correspond to an initial popping period (e.g., thestarting point, FIG. 39). The coefficient of variation of efficiencymeasured during the still phase may be utilized to define a threshold(e.g., threshold 843, FIG. 40) indicative of a popping state of thepopcorn (step 844). In some embodiments, the coefficient of variation ofefficiency measured during the still phase may be stored to memory priorto defining the threshold. Alternatively, the threshold may be definedby a predetermined value stored to memory. Once the threshold isdefined, the controller 14 monitors the coefficient of variation ofefficiency (step 846), and if the coefficient of variation of efficiencyis greater than or equal to the threshold for a predetermined period oftime (step 848), the controller 14 adjusts a power level of amplifiers18A-D (e.g., changing a duty cycle, input power, etc.) (step 850).Otherwise, the controller 14 continues to monitor the coefficient ofvariation of efficiency (step 846) until the condition specified at step848 is satisfied. With respect to step 850, the adjustment may includeadjusting (e.g., maintaining or decreasing) the power level ofamplifiers 18A-D and may also include assigning a time limit.Optionally, once the condition specified at step 848 is satisfied, or inother words, the controller 14 has detected that the popcorn is in thepopping state, the controller 14 may output a notification to the userinterface 28 or a mobile device such as a smartphone (step 852). Inresponse, a user may provide input to the controller 14 (via the userinterface 28 or the mobile device) accepting the adjustments describedfor step 850 or otherwise making other adjustments, if desired.

Subsequent to the completion of method 840, the end of the poppingprocess may be detected in response to the coefficient of variation ofefficiency being below the threshold for a predetermined amount of time.As shown in FIG. 42, method 860 begins with the controller 14 measuringthe coefficient of variation of efficiency (step 862). The controller 14monitors the coefficient of variation of efficiency (step 864), and ifthe coefficient of variation of efficiency falls below the thresholddefined in step 844 of method 840 (step 866) for a predetermined periodof time, the controller 14 adjusts (e.g., decreases) the power level andmay also assign a time limit in which to end the popping process (step868). Alternatively, the controller 14 may stop the popping processimmediately. Otherwise, the controller 14 continues to monitor thecoefficient of variation of efficiency (step 864) until the conditionspecified at step 866 is satisfied. Optionally, once the conditionspecified at step 866 is satisfied, or in other words, the controller 14has detected that the popping of the popcorn has completed or is nearcompletion, the controller 14 may output a notification to the userinterface 28 or a mobile device such as a smartphone (step 870). Inresponse, a user may provide input to the controller 14 (via the userinterface 28 or the mobile device) accepting the adjustments describedat step 868 or otherwise making other adjustments to the power leveland/or time limit, if desired.

Advantageously, the methods 840 and 860 described above enable thesystem 10 to automatically pop popcorn without burning or undercookingthe popcorn. Furthermore, by allowing the user to make adjustments tothe power level and/or time limit, the user may fine tune the automaticpopping feature to his or her liking.

A method of detecting a change in a Q-factor of the system 10 is nowdescribed with reference to FIG. 43. The system 10 may correspond to aradio frequency (RF) system that may be locally modeled as a linearpassive time-invariant system equivalent to an RLC circuit. Suchmodeling may correspond to a Foster representation of admittance. Thecircuit equivalent may correspond to a Resistor/Inductor/Capacitor (RLC)equivalent that varies based on a size of the cooking cavity 14, feedingsystem (e.g. RF feed 26A-D, 226A-D positioning), type of food load(material and temperature), as well as food load size and displacement.As the food load is heated, resonances (RLC circuits) shift and theQ-factor changes due to its relation to the equivalent RLC circuit. Theequation for the Q-factor is shown as Equation 4.

$\begin{matrix}{Q = {\frac{1}{R}\sqrt{\frac{L}{C}}}} & \left( {{Equation}\mspace{14mu} 4} \right)\end{matrix}$

The system 10 may be further configured to scan the cooking cavity 20 bymonitoring the reflection signal to model the system response accordingto spectromodal theory.

For example, based on the reflected signals from the RF feeds 26A-D,226A-D, the permittivity c of the system 10 may be identified.Additionally, the loss tangent of the system 10 may be calculated as theratio between an imaginary permittivity component ε″ and a losslesspermittivity component ε′, wherein the lossless permittivity componentis a product of a free space permittivity and a relative permittivity.The equation for the loss tangent is shown as Equation 5.

$\begin{matrix}{{\tan \mspace{14mu} \delta} = \frac{ɛ^{''}}{ɛ^{\prime}}} & \left( {{Equation}\mspace{14mu} 5} \right)\end{matrix}$

Based on the loss tangent, the Q-factor may be calculated as the inverseof the loss tangent as shown in Equation 6.

$\begin{matrix}{Q = \frac{1}{\tan \mspace{11mu} \delta}} & \left( {{Equation}\mspace{14mu} 6} \right)\end{matrix}$

In this way, the controller 14 may be operable to calculate the Q-factorbased on the reflected signals from the RF feeds. Further detailsdescribing methods of modeling resonant cavities are discussed inKurokawa, K., ed. An Introduction to the Theory of Microwave Circuits.publication: Academic Press, 2012, the entirety of which is incorporatedherein by reference.

Accordingly, based on the reflected signals from the RF feeds, thecontroller 14 may identify various spectromodal characteristics of thecavity 20. In this way, the system 10 may determine and store poles(i.e. resonance frequencies) and map the Q-factor of the cooking cavity20 in the frequency/phase domain. The system 10 may initially scan andmap the Q-factor at the beginning of a cooking operation. The system 10may further repeat the scan and map the Q-factor after a predeterminedamount of time or when a change in the reflection pattern is detected.

By comparing the changes in the Q-factor over time, the system 10 isoperable to quantify the amount of variation in the system 10 due tochanges in the food load (e.g. temperature rise due to dielectricheating). In this way, the system can detect various changes in the foodload for one or more automatic cooking functions.

With reference to FIG. 43, a method 900 is provided for controllingcooking in an electromagnetic cooking device 10 having an enclosedcavity 20 in which a food load is placed and a plurality of RF feeds26A-D, 226A-D configured to introduce electromagnetic radiation into theenclosed cavity 20 to heat up and prepare the food load, the pluralityof RF feeds 26A-D, 226A-D configured to allow measurement of forward andbackward power at the plurality of RF feeds 26A-D, 226A-D. The methodmay be executed by controller 14 and comprises: selecting a heatingtarget corresponding to an amount of energy that is to be delivered tothe food load positioned in the enclosed cavity 20 (step 902);generating a heating strategy based on the heating target to determine asequence of desired heating patterns, the heating strategy having aselected sequence of resonant modes for energy transfer into theenclosed cavity 20 that corresponds to the sequence of desired heatingpatterns (step 904); causing the RF feeds 26A-D, 226A-D to output aradio frequency signal of a selected frequency, a selected phase valueand a selected power level to thereby excite the enclosed cavity with aselected set of phasors for a set of frequencies corresponding to eachresonant mode of the selected sequence of resonant modes to createheating patterns (step 906); monitoring the created heating patternsbased on the forward and backward power measurements at the RF feeds26A-D, 226A-D to measure resonances in the enclosed cavity usingspectromodal identification and storing a map of efficiency in frequencyand phase domains in which the controller identifies resonant modes andQ-factors associated with each of the identified resonant modes (step908); determine if a specified change is detected in at least oneQ-factor (step 910); and when the specified change in the at least oneQ-factor is identified, stopping cooking of the food load using thegenerated heating strategy (step 912) otherwise continuing excite thecavity in accordance with the heating strategy and monitoring theQ-factor in steps 906-910.

The specified change in Q-factor may be when the Q-factor changes to aQ-factor that is indicative of completion of thawing. Specifically, thespecified change in Q-factor may be when the Q-factor changes to beequal to about 8. It should be noted that the Q-factor of ice is about300 and the Q-factor of water is about 8. Thus, a food load that hasthawed will have a Q-factor of about 8. Accordingly, by monitoring theQ-factor, the electromagnetic cooking device 10 may implement anautomatic defrost function that does not require the user to input thefood type or food mass.

Also, by monitoring the Q-factor, the electromagnetic cooking device 10may automatically determine when cooking of the food load is completed.In this case, the specified change in Q-factor is when the Q-factorchanges to a Q-factor that is indicative of completion of cooking. TheQ-factor that is indicative of completion of cooking may be determinedby the user inputting an identification of the food type via userinterface 28. Controller 14 may then select the heating target andgenerate the heating strategy based upon this identification of the foodload. In addition, the controller may select a pre-stored map ofefficiency showing resonance modes corresponding to a completely cookedfood load of the type of the identified food load, identify Q-factors ofthe resonance modes in the pre-stored map, and compare the maps ofefficiency stored during the cooking process to the pre-stored map todetermine when the at least one Q-factor changes to a Q-factor that isidentified from the pre-stored map, which is indicative of completion ofcooking.

Referring now to FIGS. 44, 45, and 46, plots are shown demonstrating therelative permittivity, loss tangent, and Q-factor for a plurality offood types. Referring first to FIGS. 44A, 44B, and 44C, experimentalresults for a bread or grain based food load are shown. The experimentalresults include a relative permittivity in FIG. 44A, a loss tangent inFIG. 44B, and a Q-factor in FIG. 44C for the bread in relation to atemperature of the bread. Each of the plots may demonstrate indicationsof various properties that may be utilized to identify a level ofdoneness or a cooking level of the bread. As discussed herein, donenessor a cooking level may correspond to a temperature that may indicate acompletion of heating a food load to a desired level in the cookingcavity 20. Accordingly, in various embodiments, the controller 14 maydetermine a cooking temperature or level of preparation or donenessindependent of an elapsed cooking time and independent of a startingtemperature of the food load.

From the results demonstrated in one or more of FIGS. 44A, 44B, and 44C,the controller 14 may identify the level of doneness in the form of achemical change or physical change in the food load. Referring to FIG.44C, the Q-factor maintains a relatively consistent change over thetemperatures from approximately 25° C. to 45° C. Then, between thetemperatures of 47° C. and 53° C., the Q-factor changes rapidly.Accordingly, by monitoring the Q-factor for the food load, thecontroller 14 may identify a change in the Q-factor exceeding apredetermined change threshold. More particularly, the controller 14 maymonitor the Q-factor to identify a decrease in the Q-factor exceeding apredetermined change threshold over a first change 922. In this case, inresponse to an indication that the food load comprises bread, thecontroller may monitor the Q-factor for a decrease in the Q-factor fromapproximately 1.05 to 0.85 or a change exceeding a decrease threshold ofat least 0.1, which may occur over a predetermined period of time.

Because the Q-factor changes more rapidly over the first change 922 thanduring other periods of the cooking process, the controller 14 mayidentity an increase in the rate of change of the Q-factor exceeding apredetermined threshold for bread. Accordingly, the controller 14 mayconsistently identify the first change 922 in the bread andautomatically stop or adjust the cooking cycle in response to thedetection of the first change 922. In this specific example of thebread, the first change 922 may correspond to a first gas development ofa yeast of the bread. Accordingly, in response to identifying the firstchange 922, the controller may identify first gas development of a yeastof the bread and adjust or stop a cooking cycle.

Note that the specific temperatures noted in FIGS. 44, 45, and 46 may beapproximate. Accordingly, the specific temperature ranges (e.g. thefirst range 922) and others discussed herein may only be approximatelythe same as a known temperatures corresponding to a first gasdevelopment of a yeast and other physical and/or chemical changesdiscussed herein as being detected by the controller 14. However, thisapparent error only demonstrates the strength of utilizing the Q-factorto detect the changes in the food load without the error demonstrated inthe experimental results. In other words, the controller 14 may monitorthe Q-factor to more accurately detect the changes in the physicaland/or chemical structure of the food load than by utilizing atemperature probe like that utilized to gather the experimental resultsin FIGS. 44, 45, and 46. Also, though discussed in reference to specificfoods and temperatures, the disclosure may provide for automaticdetection of various properties of various food loads and theirconstituent ingredients.

Still referring to FIG. 44C, the controller may further identify asecond change 924 in the Q-factor. More particularly, the controller 14may monitor the Q-factor to identify an increase in the Q-factorexceeding a predetermined change threshold over the second change 922.In this case, in response to an indication that the food load comprisesbread, the controller may first monitor the Q-factor the first change922. Next the controller may monitor the food load for the second change924 or an increase a decrease in the Q-factor from approximately 0.8 to1 or 0.9 to 0.98 indicating an increase in the Q-factor exceeding anincrease threshold of at least 0.1, which may occur in a predeterminedperiod of time. For bread, the second change 924 may correspond to aconcurrent enzymatic effect and starch gelatinization occurring over themeasured temperatures of approximately 66° C.-71° C. Again, in responseto the identification of the second change 924, the controller mayautomatically stop or adjust the cooking cycle.

Referring now to FIGS. 45A, 45B, and 45C, experimental results for abeef or meat based food load are shown. The experimental results includea relative permittivity in FIG. 45A, a loss tangent in FIG. 45B, and aQ-factor in FIG. 45C for the beef in relation to a temperature of thebeef. Each of the plots may demonstrate indications of variousproperties that may be utilized to identify a level of doneness or acooking level of the beef. From the results demonstrated in on or moreof FIGS. 45A, 45B, and 45C, the controller 14 may identify the level ofdoneness in the form of a chemical change or physical change in the foodload.

Referring to FIG. 45C, the Q-factor maintains a relatively consistentchange over the temperatures from approximately 20° C. to 80° C. Then,between the temperatures of 80° C. and 90° C., the Q-factor changesrapidly. Accordingly, by monitoring the Q-factor for the food load, thecontroller 14 may identify a change in the Q-factor exceeding apredetermined change threshold. More particularly, the controller 14 maymonitor the Q-factor to identify an increase in the Q-factor exceeding apredetermined change threshold over a third change 932. In this case, inresponse to an indication that the food load comprises beef, thecontroller may monitor the Q-factor for an increase in the Q-factor fromapproximately 0.6 to 1.1 or a change exceeding an increase threshold ofat least 0.4, which may occur over a predetermined period of time. Inthis way, the controller may detect a level of doneness of the beefindependent of an initial temperature of the beef and also independentof a total cooking time elapsed to cook the beef.

Because the Q-factor changes more rapidly over the third change 932 thanduring other periods of the cooking process, the controller 14 mayidentity an increase in the rate of change of the Q-factor exceeding apredetermined threshold for beef. Accordingly, the controller 14 mayconsistently identify the third change 932 in the beef and automaticallystop or adjust the cooking cycle in response to the detection of thethird change 932. In this specific example of the beef, the third change932 may correspond to a protein denaturation of the beef. Accordingly,in response to identifying the third change 932, the controller 14 mayidentify protein denaturation of a meat and adjust or stop a cookingcycle.

Referring now to FIGS. 46A, 46B, and 46C, experimental results for apotato or food load containing potato starch are shown. The experimentalresults include a relative permittivity in FIG. 46A, a loss tangent inFIG. 46B, and a Q-factor in FIG. 46C for the potato in relation to atemperature of the potato. Each of the plots may demonstrate indicationsof various properties that may be utilized to identify a level ofdoneness or a cooking level of the potato. From the results demonstratedin on or more of FIGS. 45A, 45B, and 45C, the controller 14 may identifythe level of doneness in the form of a chemical change or physicalchange in the food load.

Referring to FIG. 46C, the Q-factor maintains a relatively consistentchange in the form of a gradual decrease over the temperatures fromapproximately 20° C. to 60° C. Then, between the temperatures of 60° C.and 65° C., the Q-factor changes direction and increases. Accordingly,by monitoring the Q-factor for the food load, the controller 14 mayidentify a change in the Q-factor exceeding a predetermined changethreshold or a change in a rate of change or direction of the change inthe Q-factor. More particularly, the controller 14 may monitor theQ-factor to identify an increase in the Q-factor exceeding apredetermined change threshold over a fourth change 942. In this case,in response to an indication that the food load comprises potato, thecontroller 14 may monitor the Q-factor for an increase in the Q-factorfrom approximately 1.4 to 1.7 or a change exceeding an increasethreshold of at least 0.2 in a predetermined period of time. In thisway, the controller 14 may detect a level of doneness of the potatoindependent of an initial temperature of the potato and also independentof a total cooking time elapsed to cook the potato.

Because the trend in the Q-factor changes in direction and rate over thefourth change 942, the controller 14 may identity an increase in therate of change of the Q-factor exceeding a predetermined threshold forthe potato. Accordingly, the controller 14 may consistently identify thefourth change 932 in the potato and automatically stop or adjust thecooking cycle in response to the detection of the fourth change 942. Inthis specific example of the potato, the fourth change 942 maycorrespond to a starch gelatinization of the potato starch. Accordingly,in response to identifying the fourth change 942, the controller 14 mayidentify starch gelatinization of the potato starch and adjust or stop acooking cycle.

Referring now to FIG. 47, a method 950 of identifying a level ofdoneness of a food load based on a calculated Q-factor is discussed infurther detail. The method 950 may begin by controlling a frequency andphase of the RF signals in step 952. In step 954, the controller 14 maycontrol the high power amplifiers 18A-D generating at least a first RFfeed and a second RF feed and emit the RF feeds in the cooking cavity20. The controller 14 may additionally receive an indication of a foodtype of the food load in step 956. Based on the food type, thecontroller 14 may identify a Q-factor threshold or predetermined changethreshold from memory corresponding to a level of doneness or cookinglevel of the food type. Once the cooking process has begun, in step 958,the controller 14 may measure at least one reflection signal from thecooking cavity 20 and calculate a Q-factor based on the reflectionsignal. The reflection signal may correspond to an indication of theforward and backward (or reflected) power magnitudes in the cavity 14.

From the calculation of the Q-factor, the controller 14 may monitor theQ-factor to identify a change in the Q-factor exceeding a predeterminedchange threshold in step 960. Though described generally as apredetermined change threshold, the predetermined change threshold maycorrespond to a predetermined rate of change, predetermined direction(increase or decrease) of a rate of change, and/or a predeterminedchange or sequence of changes in reference to a current direction,trend, or rate of change of the Q-factor. Some examples of detections ofrates and directions (increases or decreases) in rates of change arediscussed in reference to FIGS. 44, 45, and 46. If the change in theQ-factor does not exceed the predetermined threshold, the method 950 mayreturn to step 958. If the change in the Q-factor does exceed thepredetermined threshold, the controller 14 may identify that the foodload has reached a level of completion or a doneness conditionidentified based on the particular food type indicated in step 956. Inthis way, the controller 14 may be operable to detect a level ofdoneness of the food load independent of an initial temperature of thefood load and also independent of a total cooking time elapsed to cookthe food load.

Although the above methods are described as being performed bycontroller 14, all or portions of the methods may be performed by RFcontrol 32 or any other controller, microprocessor, microcontroller,logic circuit, or programmed gate array, either separately or incombination.

For purposes of this disclosure, the term “coupled” (in all of itsforms, couple, coupling, coupled, etc.) generally means the joining oftwo components (electrical or mechanical) directly or indirectly to oneanother. Such joining may be stationary in nature or movable in nature.Such joining may be achieved with the two components (electrical ormechanical) and any additional intermediate members being integrallyformed as a single unitary body with one another or with the twocomponents. Such joining may be permanent in nature or may be removableor releasable in nature unless otherwise stated.

It is also important to note that the construction and arrangement ofthe elements of the device as shown in the exemplary embodiments isillustrative only. Although only a few embodiments of the presentinnovations have been described in detail in this disclosure, thoseskilled in the art who review this disclosure will readily appreciatethat many modifications are possible (e.g., variations in sizes,dimensions, structures, shapes and proportions of the various elements,values of parameters, mounting arrangements, use of materials, colors,orientations, etc.) without materially departing from the novelteachings and advantages of the subject matter recited. For example,elements shown as integrally formed may be constructed of multiple partsor elements shown as multiple parts may be integrally formed, theoperation of the interfaces may be reversed or otherwise varied, thelength or width of the structures and/or members or connector or otherelements of the system may be varied, the nature or number of adjustmentpositions provided between the elements may be varied. It should benoted that the elements and/or assemblies of the system may beconstructed from any of a wide variety of materials that providesufficient strength or durability, in any of a wide variety of colors,textures, and combinations. Accordingly, all such modifications areintended to be included within the scope of the present innovations.Other substitutions, modifications, changes, and omissions may be madein the design, operating conditions, and arrangement of the desired andother exemplary embodiments without departing from the spirit of thepresent innovations.

It will be understood that any described processes or steps withindescribed processes may be combined with other disclosed processes orsteps to form structures within the scope of the present device. Theexemplary structures and processes disclosed herein are for illustrativepurposes and are not to be construed as limiting.

It is also to be understood that variations and modifications can bemade on the aforementioned structures and methods without departing fromthe concepts of the present device, and further it is to be understoodthat such concepts are intended to be covered by the following claimsunless these claims by their language expressly state otherwise.

The above description is considered that of the illustrated embodimentsonly. Modifications of the device will occur to those skilled in the artand to those who make or use the device. Therefore, it is understoodthat the embodiments shown in the drawings and described above is merelyfor illustrative purposes and not intended to limit the scope of thedevice, which is defined by the following claims as interpretedaccording to the principles of patent law, including the Doctrine ofEquivalents.

1. A method for analyzing a frequency response of an electromagnetic cooking device comprising a resonant cavity comprising: controlling a plurality of RF signals comprising a first RF signal and a second RF signal within an operating range of the cooking device at a plurality of phase shifts between the first RF signal and the second RF signal; measuring a plurality of efficiencies of at least one reflection signal in the resonant cavity in response to a plurality of RF feeds generated from the RF signals for the plurality of phase shifts; modeling the frequency response of the resonant cavity with a numeric model; calculating a plurality of interpolation parameters for the numeric model based on the plurality of measured efficiencies of the RF feeds in response to the plurality of phase shifts; and estimating a frequency response of the cavity for the operating range of the cooking device based on the numeric model with the plurality of interpolation parameters.
 2. The method according to claim 1, further comprising: amplifying the RF signals and generating a plurality of RF feeds; and emitting the RF feeds into the cavity.
 3. The method according to claim 2, wherein the frequency response comprises a plurality of resonant modes corresponding to resonant frequencies of the cavity induced by the RF feeds.
 4. The method according to claim 2, further comprising: mapping the frequency response of the resonant cavity induced by the RF feeds in response to at least three phase shifts within the operating range of the cooking device.
 5. The method according to claim 1, wherein the plurality of phase shifts between the first RF signal and the second RF signal comprise at least three phase shifts.
 6. The method according to claim 5, wherein the measuring of the plurality of efficiencies comprises measuring at least three efficiencies corresponding to the at least three phase shifts.
 7. The method according to claim 1, wherein the efficiencies of the plurality of phase shifts are measured sequentially thereby identifying the plurality of efficiencies.
 8. The method according to claim 1, wherein the interpolation parameters correspond to coefficients of the numeric model.
 9. The method according to any one of claims 1-8, further comprising: identifying at least one resonant mode as localized maxima from the efficiency of the resonant cavity and calculated based on the numeric model with the plurality of interpolation parameters.
 10. An electromagnetic cooking device comprising: an enclosed cavity configured to receive a food load; a plurality of amplifiers configured to amplify a first RF signal and a second RF signal thereby supplying a plurality of RF feeds to the enclosed cavity; at least one measurement device configured to measure a plurality of reflection signals from the RF feeds; a controller in communication with the plurality of amplifiers and the measurement device, the controller configured to: control the first RF signal and the second RF signal within an operating range of the cooking device at a plurality of phase shifts between the first RF signal and the second RF signal; control the amplifiers to amplify the RF signals thereby generating the plurality of RF feeds; measure a plurality of efficiencies of the reflection signals in the cavity induced by the RF feeds for the plurality of phase shifts; and estimate efficiency results for the frequency response of the cavity comprising additional phase shifts estimated for the operating range of the cooking device, wherein the additional phase shifts are different from the plurality of phase shifts.
 11. The device according to claim 10, wherein the controller is further configured to: identify at least one resonant mode as a localized maxima from the efficiency results.
 12. The device according to claim 10, wherein the controller estimates the efficiency results based on a numeric model comprising a plurality of interpolation parameters.
 13. The device according to claim 12, wherein the controller is further configured to: calculate the interpolation parameters for the numeric model based on the plurality of efficiencies measured for the reflection signals.
 14. The device according to claim 12, wherein the interpolation parameters are updated by the controller for the cavity for a food load.
 15. The device according to claim 12, wherein the controller is further configured to: update the interpolation parameters during a cooking process based on additional efficiencies of the reflection signals measured by the at least one measurement device.
 16. The device according to claim 15, wherein the updated interpolation parameters are configured to improve the estimate of the efficiency results by accounting for changes in the cavity and the food load during the cooking process.
 17. An electromagnetic cooking device comprising: an enclosed cavity configured to receive a food load; a plurality of amplifiers configured to amplify a first RF signal and a second RF signal thereby supplying a plurality of RF feeds to the enclosed cavity; at least one measurement device configured to measure a plurality of reflection signals from the RF feeds; and a controller in communication with the plurality of amplifiers and the measurement device, the controller configured to: control the first RF signal and the second RF signal within an operating range of the cooking device at a plurality of phase shifts between the first RF signal and the second RF signal; control the amplifiers to amplify the RF signals thereby generating a plurality of RF feeds; measure a plurality of efficiencies of the reflection signals in the cavity induced by the RF feeds for the plurality of phase shifts; model the frequency response of the cavity with a numeric model; calculate a plurality of interpolation parameters for the numeric model based on the plurality of measured efficiencies; and generate estimated efficiency results with the numeric model for a frequency response of the cavity, wherein the estimated efficiency results comprise additional phase shifts estimated for the operating range of the cooking device, wherein the additional phase shifts are different from the plurality of phase shifts.
 18. The device according to claim 17, wherein the efficiencies of the plurality of phase shifts are measured sequentially thereby identifying the plurality of efficiencies.
 19. The device according to claim 17, wherein the plurality of phase shifts between the first RF signal and the second RF signal comprise at least three phase shifts.
 20. The device according to claim 17, wherein the controller is further configured to: identify at least one resonant mode as localized maxima from the estimated efficiency results. 